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Visible Light Communication, Networking andSensing: A Survey,
Potential and Challenges
Parth H. Pathak∗, Xiaotao Feng,†, Pengfei Hu,∗, Prasant
Mohapatra∗∗Computer Science Department, †Electrical and Computer
Engineering Department,
University of California, Davis, CA, USA.Email: {phpathak,
xtfeng, pfhu, pmohapatra}@ucdavis.edu
F
Abstract—The solid-state lighting is revolutionizing the
indoorillumination. Current incandescent and fluorescent lamps
arebeing replaced by the LEDs at a rapid pace. Apart from
ex-tremely high energy efficiency, the LEDs have other
advantagessuch as longer lifespan, lower heat generation and
improvedcolor rendering without using harmful chemicals. One
additionalbenefit of LEDs is that they are capable of switching to
differentlight intensity at a very fast rate. This functionality
has given riseto a novel communication technology (known as Visible
LightCommunication - VLC) where LED luminaires can be used forhigh
speed data transfer. This survey provides a technologyoverview and
review of existing literature of visible light com-munication and
sensing.
This paper provides a detailed survey of (1) visible
lightcommunication system and characteristics of its various
com-ponents such as transmitter and receiver, (2) physical
layerproperties of visible light communication channel,
modulationmethods and MIMO techniques, (3) medium access
techniques,(4) system design and programmable platforms and (5)
visiblelight sensing and application such as indoor localization,
ges-ture recognition, screen-camera communication and
vehicularnetworking. We also outline important challenges that need
tobe addressed in order to design high-speed mobile networksusing
visible light communication.
1 INTRODUCTIONThe indoor lighting is going through a revolution.
Theincandescent bulb that has been widely used to lit
oursurroundings since its invention over a century ago isslowly
being phased out due to its extremely low energyefficiency. Even in
the most modern incandescent bulbs,no more than 10% of the
electrical power is convertedto useful emitted light. The compact
fluorescent bulbsintroduced in 1990s have gained increasing
popularity inthe last decade as they provide a better energy
efficiency(more lumens per watt). However, recent advancementsin
solid-state lighting through Light Emitting Diodes(LEDs) have
enabled unprecedented energy efficiencyand luminaire lifespan.
Average luminous efficacy (howmuch electricity is used to provide
the intended illu-mination) of best-in-class LEDs is as high as 113
lu-
mens/watt in 2015 [1], and is projected to be around200
lumens/watt by the year 2020. This is a many foldincrease compared
to current incandescent and fluores-cent bulbs which provide an
average luminous efficacyof 15 and 60 lumens/watt [1] respectively.
Similarly, thelifespan of LEDs ranges from 25,000 to 50,000 hours-
significantly higher than compact fluorescent (10,000hours). Apart
from the energy savings and lifespanadvantages, the LEDs also have
other benefits like com-pact form factor, reduced usage of harmful
materials indesign and lower heat generation even after long
periodof continuous usage. Due to these benefits, LED adoptionis on
a consistent rise and it is expected that nearly 75%of all
illumination will be provided by LEDs by the year2030 [1].
The rapid increase in the usage of LEDs has provideda unique
opportunity. Different from the older illumi-nation technologies,
the LEDs are capable of switchingto different light intensity
levels at a very fast rate. Theswitching rate is fast enough to be
imperceptible by ahuman eye. This functionality can be used for
commu-nication where the data is encoded in the emitting lightin
various ways. A photodetector (also referred as alight sensor or a
photodiode) or an image sensor (matrixof photodiodes) can receive
the modulated signals anddecode the data. This means that the LEDs
can servedual purpose of providing illumination as well as
com-munication. In last couple of years, VLC research hasshown that
it is capable of achieving very high data rates(nearly 100 Mbps in
IEEE 802.15.7 standard and uptomultiple Gbps in research). The
communication throughvisible light holds special importance when
comparedto existing forms of wireless communications. First,
withthe exponential increase of mobile data traffic in last
twodecades has identified the limitations of RF-only mo-bile
communications. Even with efficient frequency andspatial reuse, the
current RF spectrum is proving to bescarce to meet the
ever-increasing traffic demand. Com-pared to this, the visible
light spectrum which includeshundreds of terahertz of license free
bandwidth (seeFig. 1) is completely untapped for communication.
The
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300 MHz 300 GHz 430 THz 790 THz 30 PHz 30 EHz
Microwave Infrared Visible Ultraviolet X-ray Gamma
105 m 1 mm 750 nm 380 nm 10 nm 0.01 nm Wavelength
Frequency
VioletBlueGreenYellowOrangeRed
Radio
3 KHz
1 m
Fig. 1: Human eye can perceive the electromagnetic signals
between the frequency range of 430 THz and 790 THzwhich is referred
as the visible light spectrum.
Visible Light Communication (VLC) can complement theRF-based
mobile communication systems in designinghigh-capacity mobile data
networks. Second, due to itshigh frequency, visible light cannot
penetrate throughmost objects and walls. This characteristic allows
oneto create small cells of LED transmitters with no inter-cell
interference issues beyond the walls and partitions.It can also
increase the capacity of available wirelesschannel dramatically.
The inability of signals to penetratethrough the walls also
provides an inherent wirelesscommunication security. Third, VLC
facilitates the reuseof existing lighting infrastructure for the
purpose ofcommunication. This means that such systems can be
de-ployed with relatively lesser efforts and at a lower cost.This
untapped potential of visible light communicationhas motivated us
to compile this survey.
The pioneering efforts of utilizing LEDs for illumi-nation as
well as communication date back to year2000 when researchers [2] in
Keio University in Japanproposed the use of white LED in homes for
buildingan access network. This was further fueled by rapid
re-search, especially in Japan, to build high-speed commu-nication
through visible light with development of VLCsupport for hand-held
devices and transport vehicles.This led to formation of Visible
Light CommunicationsConsortium (VLCC) [3] in Japan in November of
2003.VLCC proposed two standards - Visible Light Commu-nication
System Standard and Visible Light ID SystemStandard - by 2007.
These standards were later acceptedby Japan Electronics and
Information Technology In-dustries Association (JEITA) [4] as JEITA
CP-1221 andCP-1222 respectively. The VLCC also incorporated
andadapted the infrared communication physical layer pro-posed by
international Infrared Data Association (IrDA)[5] in 2009. In
parallel, hOME Gigabit Access project(OMEGA) [6], sponsored by
European Union, also de-veloped optical communication as a way to
augmentthe RF communication networks. In 2014, VLCA (VisibleLight
Communications Associations) [7] is established asa successor of
VLCC in Japan for further standardizationof VLC. The first IEEE
standard for visible light com-munication was proposed in 2011 in
the form of IEEE802.15.7 [8] which included the link layer and
physical
layer design specifications. In last couple of years,
theachievable VLC link capacity has surpassed 1 Gbps, andincreasing
research efforts are being directed towardsrealizing the full
potential of VLC.
In this survey, we provide a systematic view of VLCresearch and
identify important challenges. Specifically,we provide technology
overview and literature reviewof
1) Visible light communication system componentsand, details of
transmitter and receiver characteris-tics,
2) Physical layer characteristics such as channelmodel and
propagation, modulation and cod-ing schemes, and Multiple-Input
Multiple-Output(MIMO) techniques,
3) Link layer, multiple user access techniques andissues,
4) System design and various programmable VLCplatforms,
5) Visible light sensing and applications such as vis-ible light
indoor localization, human computer in-teraction, device-to-device
communication and ve-hicular communication applications.
Based on the review, we then outline a list of challengesthat
need to be addressed in future research to realizefull potential of
VLC.
The growing interest in VLC has resulted in a fewsurveys in past
couple of years. This article differs fromthese surveys in many
ways. In [9], authors discussedLED-based VLC where the primary
focus of discussionwas on design of physical layer techniques
(modulation,circuit design etc.) that can enhance the performanceof
VLC. Compared to [9], this article focuses on abroader discussion
about VLC, covering other aspectsof networking such as medium
access as well as sensingusing visible light. Medium access
protocols for VLChave been surveyed in [10], however, no
comprehen-sive overview and comparison of networking techniqueshave
been provided. Also, in this paper, we show thatthe usage of
smartphone camera and light sensor forreceiving visible light
signals extend the VLC to otherrelated fields of mobile computing
and sensing. Multipleresearch topics in this area such as indoor
localization
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and smartphone screen-camera communication are notsurveyed in
any earlier work before this paper. In thispaper, we provide a
comprehensive survey of thesetopics with additional focus on
visible light sensing. Com-pared to [11] and [12] where authors
surveyed free-space communication along with other forms of
opti-cal wireless communications, the primary focus of thissurvey
is narrower and more detailed towards visiblelight communication.
In another related survey, authorsprovided a detailed overview of
how optical wirelesscommunication can be used for cellular network
designin [13], with different aspects of outdoor environmentand its
impact on the communication performance. Com-pared to this, our
primary focus in this paper is onvisible light communication
primarily in indoor settings.Authors provided a brief survey of VLC
applications in[14] with some discussion on vehicular networks
andindoor broadcasting. However, in this paper, we surveya growing
body of literature since the publication of [14]focusing on novel
applications of VLC such as indoorlocalization, screen-camera
communication etc. We alsodetail various practical aspects of
communication systemdesign by reviewing currently available
programmableplatforms and LED transmitters/receivers. This will
en-able researchers with RF communication backgroundto easily
extend their expertise in visible light wirelessaccess
networks.
The rest of the survey is organized as follows. We startby
providing an overview of various components of avisible light
communication system with introductionto LED luminaires and
different types of receivers inSection 2. In Section 3, we survey
the physical layerproperties of VLC with details on channel and
propaga-tion, modulation methods and MIMO techniques. It
alsoincludes an overview of VLC standard IEEE 802.15.7 [8].This is
followed by Section 4 where various link layerand medium access
protocols are discussed. Section 5describes various aspects of VLC
system design andsurveys available programmable platforms that can
beused for research. Section 6 reviews a wide variety oftopics in
visible light sensing and applications whichincludes indoor
localization, screen-camera communica-tion, vehicular communication
and human-computer in-teraction. Based on the review, Section 7
outlines variouschallenges that need further research in order to
buildhigh-capacity, mobile VLC networks. We have compiledthe
acronyms used throughout the paper and presentedthem with their
full forms in Table 1.
2 VLC SYSTEM OVERVIEWIn this section, we provide an overview of
visible lightcommunication system and its transmitter and
receivercomponents. We then discuss various modes of VLC.
2.1 VLC TransmitterThe transmitter in a visible light
communication systemis an LED luminaire. An LED luminaire is a
complete
TABLE 1: Acronyms and their full names
Acronym Full formACO-OFDM Asymmetrically-Clipped Orthogonal
Frequency Di-
vision MultiplexingADC Analog to Digital ConverterAoA Angle of
ArrivalBER Bit Error Rate
BIBD Balanced Incomplete Block DesignsCAP Contention Access
PeriodCCA Clear Channel Assessment
CC Convolutional CodingCCM Code Cycle ModulationCRC Cyclic
Redundancy CheckCSK Color Shift Keying
CSMA-CA Carrier Sense Multiple Access - Collision AvoidanceDAC
Digital to Analog Converter
DCO-OFDM Direct Current biased Optical Orthogonal Fre-quency
Division Multiplexing
DMT Discrete MultiToneDOPPM Differential Overlapping Pulse
Position Modulation
DPPM Differential Pulse Position ModulationDSRC Dedicated
Short-Range CommunicationEPPM Expurgated Pulse Position
Modulation
FEC Forward Error CorrectionFET Field Effect Transistor
FOV Field Of ViewFPS frames per second
Gbps Gigabits per secondGPS Global Positioning SystemGTS
Guaranteed Time SlotHCI Human Computer Interaction
HetNets Heterogeneous NetworksIM/DD Intensity Modulation/Direct
Detection
JT Joint TransmissionKbps Kilobits per secondLCD
Liquid-crystal-displayLED Light Emitting DiodeLOS Line Of SightLTE
Long Term Evolution
MAC Medium Access ControlMbps Megabits per secondMCS Modulation
and Coding Scheme
MEPPM Multi-level Expurgated Pulse Position ModulationMIMO
Multiple Input Multiple OutputMISO Multiple Input Single Output
MPPM Multipulse Pulse Position ModulationMU-MIMO Multiple User -
Multiple Input Multiple Output
NFC Near Field CommunicationNRZ Non Return to Zero
OCDMA Optical Code Division Multiple AccessOFDMA Orthogonal
Frequency Division Multiple Access
OFDM Orthogonal Frequency Division MultiplexingOMPPM Overlapping
Multipulse Pulse Position Modulation
OOC Optical Orthogonal CodesOOK On Off Keying
OPPM Overlapping Pulse Position ModulationPAPR Peak to Average
Power Ratio
PDP Power Delay ProfilePPM Pulse Position Modulation
PWM Pulse Width ModulationQAM Quadrature Amplitude
Modulation
RC Repetition CodingRF Radio Frequency
RGB Red Green BlueRLL Run Length Limited
RS Reed-Solomon codingRSS Received Signal Strength
RTS/CTS Request To Send/Clear To SendSFO Sampling Frequency
Offset
SISO Single Input Single OutputSLM Spatial Light ModulatorSMP
Spatial Multiplexing
SM Spatial ModulationSNR Signal to Noise RatioVLC Visible Light
Communication
VPPM Variable Pulse Position ModulationWDM Wavelength Division
Multiplexing
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lighting unit which consists of an LED lamp, ballast,housing and
other components. The LED lamp (alsoreferred as an LED bulb in
simpler terms) can includeone or more LEDs. The lamp also includes
a drivercircuit which controls the current flowing through theLEDs
to control its brightness. When an LED luminaireis used for
communication, the driver circuit is modified(further details in
Section 5) in order to modulate thedata through the use of emitted
light. For example, in asimple On-Off Keying modulation, the data
bit “0” and“1” can be transmitted by choosing two separate levelsof
light intensity.
A crucial design requirement for VLC system is thatillumination,
which is the primary purpose of the LEDluminaries, should not be
affected because of the com-munication use. Hence, performance of
the VLC systemis also affected depending on how the LED
luminairesare designed. White light is by far the most commonlyused
form of illumination in both indoor as well asoutdoor applications.
This is because colors of objects(also known as color rendering) as
seen under the whitelight closely resemble the colors of the same
objectsunder the natural light. In solid-state lighting, the
whitelight is produced in following two ways -
1) Blue LED with Phosphor: In this method, thewhite light is
generated by using a blue LED thathas yellow phosphor coating. When
the blue lighttraverses through the yellow coating, the
combina-tion produces a white light. Different variations ofthe
white light (color temperatures) are producedby modifying the
thickness of the phosphor layer.
2) RGB Combination: White light can also producedby proper
mixing of red, green and blue light. Inthis method, three separate
LEDs are used whichincreases the cost of LED luminaire compared
tousing the Blue LED with Phosphor.
Due to ease of implementation and lower cost, thefirst method
with blue LED and phosphor is morecommonly used for designing white
LED. However, interms of communication, the phosphor coating limits
thespeed at which LED can switched to a few MHz. Aswe will discuss
in Section 3.2, various solutions havebeen proposed to alleviate
this limitation. On the otherhand, RGB combination is preferable
for communicationas it also creates an opportunity of using Color
ShiftKeying to modulate the data using three different
colorwavelength LEDs.
2.2 VLC Receiver
Two types of VLC receivers can be used to receive thesignal
transmitted by an LED luminaire
1) photodetector - also referred as photodiode or non-imaging
receiver,
2) imaging sensor - also called a camera sensor.The
photodetector is a semiconductor device that con-verts the received
light into current. The current com-
mercial photodetectors can easily sample the receivedvisible
light at rates of tens of MHz.
An imaging sensor or a camera sensor can also be usedto receive
the transmitted visible light signals. Becausesuch camera sensors
are available on most of today’smobile devices like smartphones to
capture videos andimages, it has the potential to convert the
mobile devicesin readily available VLC receivers. An imaging
sensorconsists of many photodetectors arranged in a matrixon an
integrated circuit. However, the limitation of animaging sensor is
that in order to enable high-resolutionphotography, the number of
photodetectors can be veryhigh. This significantly reduces the
number of framesper second (fps) that can be captured by the
camerasensor. For example, the fps of commonly used camerasensors
in smartphones is no more than 40. This meansthat direct use of
camera sensor to receive visible lightcommunication can provide
very low data rate.
The “rolling shutter” property of camera sensor can beused to
receive the data at a faster rate. Due to a largenumber of
available photodetectors in a camera sensor, itis not possible to
read the output of each pixel in parallel.Instead modern camera
sensors employ row scanningwhere photodetectors of one row of the
matrix is read ata time. This procedure of reading photodetector
outputrow by row (or column-by-column) is referred as
rollingshutter. Fig. 2a shows how the rolling shutter process canbe
leveraged to increase the data rate. For illustrationpurposes, we
assume that the transmitter uses ON-OFF modulation. The transmitter
can change its state(transmit the next symbol) in a time shorter
than the timerequired to scan a row of pixels. As shown in Fig.
2a,the transmitter is in ON state first which results in
higherintensity output for pixels of the first column. At the
nexttime instance, it changes its state by switching to OFFstate.
This can be recorded as low intensity output forpixels of the
second column. Once all the columns arescanned, all the columns of
the resultant image can beconverted to binary data. It was shown in
[16] that multi-kbps of throughput can be achieved using the
rollingshutter process of camera sensor.
Note that image sensor can allow any mobile devicewith camera to
receive visible light communication.However, in its current form,
it can only provide verylimited throughput (few kbps) due to its
low samplingrate. On the other hand, stand-alone photodetectors
haveshown to achieve significantly higher throughput (hun-dreds of
mbps). In this survey, we assume the receiverto be the
photodetector unless otherwise mentionedspecifically.
2.3 VLC Modes of Communication
Visible light communication can be classified into twomodes: (1)
Infrastructure-to-device communication and(2) Device-to-device
communication. An indoor scenariowhere LED luminaires are used to
illuminate the roomis shown in Fig. 2b. In this case, the
luminaires can
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ON OFF ON OFFTransmitter LED state
Image sensor readout
(a) The rolling shutter effect observed when receiving data
using an image sensor.
Thermostat
LED lightsSafety alarm
Television
(b) An example scenario showing that LEDs cancommunicate to
various devices including user’s
mobile devices and other smart devices;reproduced using [15]
Fig. 2: The rolling shutter effect and typical usage scenario of
an indoor VLC network
transmit data to various devices inside the room. TheLEDs can
also coordinate between themselves to reducethe interference and
even enable coordinated multi-pointtransmission to receiving
devices. The uplink transmis-sion from the devices are difficult to
achieve becauseusing LEDs on end-user devices can cause
noticeabledisturbance to users. In such case, RF or infrared
com-munication can be used for the uplink transmissions.Similar to
the indoor case, the LEDs used in street lampsas well as traffic
lights can be used to provide internetaccess to users in cars and
pedestrians. We will discusssuch vehicular application in Section
6.3.
Due to omni-present camera sensor for mobile de-vices, the
visible light communication can also be usedfor near-field
device-to-device communication. Here, theLED pixels on the display
of one smartphone can beused to transmit data to the camera sensor
of anothersmartphone. With recent advances in design of
efficientcodes, such screen-to-camera streaming has been shownto
achieve very high throughput. We discuss these tech-niques in
Section 6.2. In another form of device-to-devicecommunication, cars
and other vehicles on the road cancommunicate with each other to
form an ad-hoc networkusing VLC.
Although we discussed the vehicular networking andscreen-camera
communication, our primary focus inthis survey is towards design
and analysis of indoorinfrastructure-to-device networking using
visible light.
3 PHYSICAL LAYERWe start with a comprehensive overview of VLC
physi-cal layer by discussing (1) channel model and
character-istics, (2) modulation methods and (3) MIMO techniquesfor
VLC.
3.1 Channel Model and Propagation Characteristics
In this section, we describe the channel model for prop-agation
of visible light. Based on the channel model, it
is possible to choose an LED with appropriate specifica-tions
and estimate its communication link performance.Note that the
notations symbols used throughout thissection are listed in Table 2
with their meaning.
3.1.1 Transmitted Power of an LED - Luminous Flux
An LED transmitter serves dual purpose of illuminationand
communication. Therefore, it is necessary to firstestablish an
understanding of relevant photometric andradiometric parameters.
Using these parameters, we willbe able to calculate the Luminous
Flux which is thetransmitted power of an LED transmitter. First, we
willcalculate the transmitted power, path loss and receivedpower of
a Line-Of-Sight (LOS) link and then analyzethe multipath impact of
reflected paths.
Photometric parameters quantify the characteristics oflight
(such as brightness, color etc.) as perceived by thehuman eye. They
are useful in understanding the illumi-nation aspects of LEDs.
Radiometric parameters measurethe characteristics of radiant
electromagnetic energy oflight. They are useful in determining
communicationrelated properties of LEDs. There are two ways of
cal-culating the Luminous Flux - using spectral integral orusing
spatial integral. Depending on which parametersare available for a
given LED transmitter, one of the twomethods can be chosen for
calculation of luminous flux.
Spectral Integral: The spectral integral method usesluminosity
function of human eye and spectral powerdistribution of an LED to
derive the luminous flux.
Luminosity Function V (λ): The photopic vision of humaneye
allows humans to distinguish different colors, mak-ing it a crucial
factor in designing lighting technology[17]. It was shown in [18]
that human’s photopic visionexhibits different levels of
sensitivity to different wave-lengths of visible light spectrum.
This aspect is shownin Fig. 3 using the luminosity function V (λ).
The functionshows that human eye can see the colors within therange
of 380 nm to 750 nm with the maximum sensitivityat wavelength of
555 nm (the yellow-green region).
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TABLE 2: Symbols and their meaning
Symbol Meaningλ Wavelength
V (λ) Luminosity functiuonST (λ) Transmitter spectral power
distribution function
FT Transmitter luminous fluxFR Receiver luminous flux
gt(θ) Luminous intensity distributionI0 Axial intensity
θmax Half beam angleΩmax Full beam angleLL Luminous path lossLP
Optical power path lossD Distance between transmitter and receiverr
Radius of the receiver apertureα Incident angleβ Irradiation
angleAr Receiver aperture areaΩr Receiver solid angle from
transmitterm Order of Lambertial emission
φ1/2 Semi-angle at half illuminanceRf (λ) Spectral responsivity
functionPRo Received optical power
SR(λ) Receiver spectral power distribution functionλrL Lower
wavelength cut-off for optical filterλrH Higher wavelength cut-off
for optical filterPR(i) Received optical power from LOS link of ith
LED
PR(total) Total received optical powerρ(λ) Spectral
reflectranceN Number of LED transmittersk Number of bounces of
light
h(t) Power delay profileδ Dirac delta functionc Speed of
light
FOV Acceptance angle of receiverΓ(k)n Power of reflected ray
after kth bounce
σshot Standard deviation of shot noiseσthermal Standard
deviation of thermal noise
x Number of photons collected in unit timeκ Boltzmann’s
constantIB Photocurrent due to background noiseGol Open-loop
voltage gainTk Absolute temperature
Cpd Capacitance of the photodetector per unit areaη FET channel
noise factor
gm FET transconductanceI2, I3 Noise-bandwidth factors
Spectral Power Distribution ST (λ): The ST (λ) of an LEDis the
function representing the power of the LED atall wavelengths in the
visible light spectrum. The LEDvendors typically publish the
distribution to explainhow different colors will be rendered in the
presenceof the LED. It is a radiometric parameter measuredin
Watts/nm. The spectral power distribution of threedifferent colored
LEDs are shown in Fig. 4. It can beobserved that all three LEDs
have high radiant powerat two wavelengths - blue and yellow. As
describedin Section 2.1, most current LEDs produce white lightby
combining blue light emitted by a blue LED withyellow phosphor
coating. Depending on the desiredtype of white color (warm, natural
or cool), blue andyellow light emissions are controlled using the
phosphorcoating. For example, more yellow light is allowed inwarm
and natural white compared to the cool whiteLED.
Luminous Flux: The luminous flux combines luminos-ity function
and spectral power distribution to calculate
Hu
ma
n e
ye
se
nsitiv
ity V
(λ)
Wavelength (λ) (nm)
0.0001
0.001
0.01
0.1
1
300 400 500 600 700 800 900
Vio
let
Blu
eC
ya
n
Gre
en
Ye
llow
Ora
ng
e
Re
d
Visible spectrum
Maximum sensitivity at 555 nm
Fig. 3: Luminosity function representing human eye’ssensitivity
to different wavelengths in the visible
spectrum.
No
rma
lize
d R
ad
ian
t P
ow
er
(%)
Wavelength (λ) (nm)
Warm white
Natural white
Cool white
0
10
20
30
40
50
60
70
80
90
100
400 450 500 550 600 650 700 750
Fig. 4: Power spectral distribution for LED of threecolor types
- warm white, natural white and coolwhite. Warm white and natural
white have more
radiated power for green-yellow-orange wavelengthscompared to
cool white which provides a more bluish
illumination; Figure reproduced from [19].
the “perceived” power emitted by the LED. It weighs theST (λ)
function with V (λ) (the sensitivity of human eyeto different
wavelengths) because we know from Fig. 3that human eye does not
respond to all wavelengthsequally. The luminous flux of the
transmitter LED (FT )is measured in lumens and it can be calculated
as
FT = 683 (lumens/watt)
750 nm∫380 nm
ST (λ)V (λ)dλ (1)
The constant 683 lumens/watt is the maximum luminousefficiency.
The luminous efficiency is the ratio of luminousflux to the radiant
flux, which measures how well theradiated electromagnetic energy
and required electricityof an LED was transformed to provide
visible lightillumination. We know from Fig. 3 that human eyeis
most sensitive to detect the wavelength of 555 nm(green). The
electrical power necessary to produce onelumen of light at the
wavelength of 555 nm is derived tobe 1/683rd of a watt [20]. This
means that for any other
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color source, the power necessary to produce one lumenof light
is always higher than 1/683rd of a watt. Hence,the maximum luminous
efficiency is 683 lumens/wattwhich occurs at 555 nm wavelength.
Spatial Integral: Another way of calculating the lumi-nous flux
is to utilize LED’s spatial emission properties.For this, we will
use luminous intensity and axial inten-sity as described next.
Rela
tive
Lu
min
ou
s I
nte
nsity (
%)
Angle
LED 1LED 2
20
40
60
80
100
-100 -80 -60 -40 -20 0 20 40 60 80 100
(a)
90
45
0
300
600
900
1200
Lum
inou
s in
tens
ity (c
ande
la)
Angle
I0= 987 candela
494
max=47o
(b)
Fig. 5: (a) Luminous intensity distribution for two LED- (1)
Cree XLamp XP-E High-Efficiency White [19] (2)
Cree XLAMP XR-E [21] (b) Luminous intensitydistribution of Cree
LMH6 in polar coordinates [22]
and its half-beam angle; Figures reproduced from [19],[21],
[22].
Luminous Intensity gt(θ): While luminous flux mea-sures the
total amount of light emitted by an LED, theluminous intensity
measures how bright the LED is ina specific direction. It is
measured in Candela which isluminous flux per unit solid angle (1
steradian). Thisallows us to understand where the LED directs its
light.Fig. 5 shows the luminous intensity distribution of
threedifferent LEDs. In Fig. 5a, both the LEDs emit lightat wider
angles allowing better illumination in manydirections, while in
Fig. 5b, it can be observed that LEDemits light in a narrower beam
(much like spotlighting).Most LED sources have Lambertial beam
distribution[23] which means that the intensity drops as the
cosineof the incident angle.
There are two important parameters to be derivedfrom the
intensity distribution
Axial Intensity (I0) is defined as the luminous intensityin
candelas at 0o solid angle. For LED in Fig. 5b, the axialintensity
is 987 candela. Typically, the luminous intensitydistribution
provided by the vendors are normalizedwith the axial intensity as
shown in Fig. 5a.
Half Beam Angle (θmax) is the angle at which the lightintensity
decreases to half of the axial intensity. For theLED in Fig. 5b,
the half beam angle is 47o. For theLambertian sources like LEDs,
the half beam angle iscalculated from the entire beam angle (Ωmax)
as follows
Ωmax = 2π(1− cos θmax) (2)
The luminous flux can now be calculated by integrat-ing the
luminous intensity function over the entire beam
solid angle Ωmax. Different from Equ. (1) which was aspectral
integral, here the flux is calculated using spatialintegral as
below
FT =
Ωmax∫0
I0gt(θ)dΩ (3)
where gt(θ) is the normalized spatial luminous
intensitydistribution. Combining Equs. (2) and (3), we get
FT = I0
θmax∫0
2πgt(θ)sinθdθ (4)
3.1.2 Path Loss and Received PowerBased on the luminous flux
calculated above, we will
now derive the value of path loss. It was proven in[24] that the
path loss in photometric domain (referredas luminous path loss LL)
is the same the path lossin radiometric domain (referred as optical
power pathloss LP ). This is due to the fact that in
line-of-sightfree space propagation, the path loss can be assumedto
be independent of the wavelength. Therefore, we cancalculate LL
using the luminous flux derived in theprevious section.
Specifically, LL is the ratio of luminousflux of the receiver (FR)
and the transmitter (FT ). FT canbe calculated as Equ. (4).
max
radius (r)
Distance (D)
Transmitter
Receiver
Tran
smitt
er r
Ar
Receiver
Fig. 6: Relative position of transmitter and receiver inLOS
settings; reproduced from [24].
In order to calculate the FR, it is necessary to specifythe
relative positions of the transmitter and the receiver.This
relative positioning is shown in Fig. 6. Here, thedistance between
the receiver and the transmitter isD, and radius of the receiver
aperture is r. The anglebetween the receiver normal and
transmitter-receiverline is α (also referred as incident angle).
The transmitterviewing angle is β (also referred as irradiation
angle). Letthe receiver solid angle as observed from the
transmitterbe Ωr and receiver’s area Ar as shown in Fig. 6,
then
Arcos(α) = D2Ωr (5)
From Fig. 6, the receiver flux FR can be calculated as
FR = I0gt(β)Ωr (6)
-
8
The optical path loss LL can be calculated using Equa-tions (4),
(5) and (6) as
LL =FRFT
=gt(β)Arcosα
D2θmax∫
0
2πgt(θ)sinθdθ
(7)
Most LED sources have Lambertial beam distributionwhich means
that the spatial luminous intensity distri-bution is a cosine
function
gt(θ) = cosm(θ) (8)
where m is the order of Lambertial emission. The valueof m
depends on the semi-angle at half illuminance Φ1/2of the LED
m =ln(2)
ln(cosΦ1/2)(9)
Substituting Equ. (8) and θmax in Equ. (7), we get thepath loss
value for a Lambertian LED source as follows
LL =(m+ 1)Ar
2πD2cos α cosm(β) (10)
If the LED emission can not be modeled using theLambertian
cosine function, it is necessary to measuregt(θ) for the given LED,
and use it to calculate LL fromEqu. (7).
The received optical power can be now calculatedusing the path
loss. It is typical that the receiving pho-todetector is equipped
with an optical filter. Let Rf (λ)denote the spectral response of
the optical filter. Fig. 7shows Rf (λ) of a typical photodetector.
Using Rf (λ), the
0.1
0.2
0.3
0.4
0.5
0.6
300 400 500 600 700 800 900 1000 1100 1200
Responsiv
ity (
A/W
)
Wavelength (nm)
Fig. 7: Spectral response of a typical photodetectorreceiver;
responsivity (measured in A/W) is the ratio of
output photocurrent in amperes to incident radiantenergy in
watts; reproduced from [25].
received optical power PRO for the direct line-of-sightoptical
link can be calculated as
PRO =
λrH∫λrL
SR(λ)Rf (λ)dλ (11)
where SR(λ) = LPST (λ) = LLST (λ) and λrL and λrHare lower and
upper wavelength cut-off values for theoptical filter
respectively.
Considering Equations (10) and (11), the receivedpower is
dependent on three factors - the transmitter-receiver distance (D),
incident angle (α) and irradiation
angle (β). These three factors are independent of trans-mitter
and receiver hardware, and depend on receiver’smovement and
orientation. As an example, if the receiveris a smartphone equipped
with a photodiode, the threefactors will change based on user’s
movement and de-vice orientation. It is crucial to understand the
impact ofthese factors on received power in order to evaluate
theachievable capacity. Authors in [26] studied the impactusing a
smartphone photodiode as the receiver. Fig. 8show how the
normalized received power (measuredas light intensity on smartphone
photodiode) varieswith changes in D, α and β. Fig. 8a shows how
thereceived power attenuates with D as inverse square low(Equ.
(10)). The incident angle measures the changesin smartphone’s
orientation (0o means photodiode isdirectly facing the LED). As the
incident angle (α) in-creases, the energy at which the photons
strike the pho-todiode decreases, which in turn results in decrease
ofreceived power. Similarly, the received power decreaseswith
increase in the irradiation angle (β) confirmingthe lambertian
emission pattern of the LED. The impactof these three factors have
important implications onguaranteeing high SNR in VLC access
networks andmanaging inter-cell interference as we will discuss
inSection 4.2.
3.1.3 Multipath Propagation with Reflected PathsAs we saw in
Section 2, typically there are more than oneLED in a luminaire. The
receiving photodetector can si-multaneously receive (intensity
modulated) signals frommultiple LEDs as shown in Fig. 2b. The
received opticalpower of the receiver can be calculated by summing
thereceived power of each LOS link within receiver’s field-of-view
(FOV) can be expressed as
PR(total) =
N∑i=0
PR(i) (12)
where N is the total number of LEDs and PR(i) isthe received
optical power from LOS link of ith LEDcalculated from Equ.
(11).
Since the majority of the indoor surfaces are more orless
reflective of visible light, it is necessary to under-stand the
impact of reflected paths on the performanceof communication.
Spectral reflectance (ρ(λ)) representsreflectivity of a surface
(such as wall, ceiling etc.) asa function of wavelength. It was
noted in [27] thatreflectivity of Infrared signal is higher
compared to thevisible band. The spectral reflectance of commonly
usedbuilding materials like plaster wall, ceiling etc. wasmeasured
in [27] using a spectrophotometer. Fig. 9 showsthe results of
measured reflectivity. It can be observedthat plastic wall has the
least reflectivity while the plasterwall has the highest
reflectivity.
Because of the reflections, the receiver receives signalfrom
many different paths. Such multipath propagationcan be
characterized using Power Delay Profile (PDP).The PDP gives the
distribution of received power as a
-
9
0.96
0.76
0.57
0.38
0.19
01 2 3 4 5 6
Nor
mal
ized
rece
ived
pow
er
Distance - D (m)
Incident angle = 0Irradiance angle = 0
(a)
10.80.60.40.2
0 90 75 60 45 30 15 0
Nor
mal
ized
rece
ived
pow
er
Incident angle
Distance = 4 mIrradiance angle = 0
(b)
0.2
0.4
0.6
0.8
1
0 15 30 45 60 75
Nor
mal
ized
rece
ived
pow
er
Irradiance angle
Distance = 4 mIncident angle = 0
(c)
Fig. 8: Impact of (a) transmitter-receiver distance, (b)
incident angle (α) and (c) irradiation angle (β) on thereceived
power; reproduced from [26]
0
0.2
0.4
0.6
0.8
1
350 400 450 500 550 600 650 700 750
Sp
ectr
al re
fle
cta
nce
Wavelength (nm)
Plastic wallCeilingFloorPlaster wall
Fig. 9: Different indoor surfaces exhibit different levelsof
spectral reflectance depending on the wavelength;
reproduced from [27].
function of propagation delay. A non-LOS signal canbe bounced
from many surfaces before it reaches thereceiver photodetector as
shown in Fig. 10. Authors in
Transmitter
Receiver
1
2
01
k
k+1
2
0
k+1 FOV
D1
2Dk+1D
Firstbounce
k-thbounce
0D
Fig. 10: A non-LOS signal can bounce off the surfacesmany times
before reaching the receiver; β and α
denote the angle of irradiation and incidentrespectively;
reproduced from [27].
[27] modeled the PDP of multiple bounces for a total of
N LEDs at time instance t as
h(t) =
N∑n=1
∞∑k=0
h(k)(t;Sn) (13)
where Sn is the spectral power distribution of nth LEDand k is
the number of bounces. When k = 0, theresultant PDP [27] is that of
an LOS path as
h(0)(t;Sn) = L0Pnrect
(α0FOV
)δ
(t− D0
c
)(14)
where L0 = LL is the path loss for the LOS case (derivedin Equ.
(10)), δ is a dirac delta function, D0 is the distancebetween the
LED and the receiver and c is the speedof light. Because the
photodiode can only detect thelight whose angle of incidence is
smaller than its FOV, arectangular function [27] is used where
rect(x) =
{1 for |x| ≤ 10 for |x| > 1
This means that when if a ray does not reach within theFOV of
the receiver after k bounces, its effect on the totalreceived power
is considered 0.
When k ≥ 1, the PDP after k bounces (refer Fig. 10)for the nth
LED can be calculated [27] as
h(k)(t;Sn) =
∫s∈S
[L1L2 · · ·Lk+1Γ(k)n rect
(α0FOV
)× (15)
δ
(t− D1 +D2 + · · ·+Dk+1
c
)]dAs (16)
where
L1 =As(m+ 1) cos α1 cos
mβ1
2πD12 (17)
For the path loss of the first bounce L1, the ray origi-nated
from the LED which we have previously modeledas a Lambertian
emitter (Equ. (8)). For the remainingbounces, we can calculate the
path loss of each path as
L2 =As cos β2 cos α2
πD22 (18)
Lk+1 =AR cos βk+1 cos αk+1
πDk+12 (19)
-
10
The integration in Equ. (16) for each surface s of allreflectors
S where As is the area of the surface. For Lk+1,AR is the area of
the photodiode receiver. Γ
(k)n is power
of the reflected ray after kth bounce. It is calculated
[27]as
Γ(k)n =
∫λ
Sn(λ)ρ1(λ)ρ2(λ) . . . ρk(λ)dλ (20)
where ρk(λ) is the spectral reflectance of the surface ofkth
bounce.
43.5
32.5
21.5
10.5
00 5 10 15 20 25 30
Rec
eive
d po
wer
(W)
10-5
Time (ns)
Plaster wallPlastic wall
Fig. 11: Power delay profile for 4 LED transmitters in acubic
room with plaster or plastic walls; reproduced
from [27].
Fig. 11 shows the power delay profile in a realisticscenario
where four LED luminaires are deployed ina square topology on a
ceiling of a cubic room witheither plaster or plastic walls [27].
It can be observedthat the first peak is due to the direct received
signal(LOS) from the LED. The other peaks are due to
multiplereflections from the wall as calculated using Equ. (16).As
expected, the received power due to reflection multi-path is
relatively lesser compared to the LOS power.
Most of the power delay profiling [27]–[30] of visiblelight
communication rely on simulations. However, de-tailed
measurement-based studies in realistic scenarios(such as indoor
places with many different reflectingobjects, different LED
arrangements etc.) are necessaryfor improved understanding of
multi-path in VLC anddeveloping the techniques to combat it.
3.1.4 Receiver Noise and SNRThere are three major sources of
noise in indoor visiblelight optical link (1) ambient light noise
due to solarradiation from windows, doors etc. and noise due
toother illumination sources such as incandescent andfluorescent
lamps, (2) shot noise induced in the pho-todetector by the signal
and the ambient light and (3)electrical pre-amplifier noise (also
known as thermalnoise) of the photodetector.
The ambient noise of solar radiation and artificialillumination
sources such as lamps results in ambientnoise floor which is a DC
interference. The effect ofsuch noise can be mitigated by using a
electrical high
pass filter at the receiver. Most of the previous studiesassume
that this ambient noise floor remains stationaryover space and
time, however, no systematic evaluationis present in the
literature. For example, the indoor solarradiation changes at
different places depending on win-dows and doors. The radiation
also changes dependingon the time of the day (and year) and
orientation ofthe windows/doors. Radiation from other
illuminationsources will also remain an unavoidable source of
noiseuntil we completely transition to LED technology. Itis
required that exhaustive indoor measurements arecarried out to
accurately account for such noise.
Once the noise due to solar radiation and artificialillumination
sources is filtered, the SNR at the receivercan be calculated based
on the shot noise and the thermalnoise of the photodetector
circuitry as
SNR =PRE
2
(σshot)2 + (σthermal)2(21)
where σshot and σthermal are the standard deviation ofshot noise
and thermal noise respectively. The shot noiseis due to inherent
statistical fluctuation in the amountof photons collected by the
photodetector. It is knownthat the photon counting follows a
poisson distributionwhich means that if the mean of number of
photonscollected by the photodetector in a unit time is x, thenthe
standard deviation of number of photons collectedis√x. This also
results in poisson distributed variation
in photoelectrons generated by the photodetector. Basedon this,
the variance of shot noise can be calculated [23],[31] as below
(σshot)2 = 2qPREB + 2qIBI2B (22)
The variance of thermal noise [23], [31] is
(σthermal)2 =
8πκTkGol
CpdAI2B2 +
16π2κTkη
gmC2pdA
2I3B3
(23)where B Hz is the bandwidth of the photodetector, κ
is the Boltzmann’s constant, IB is the photocurrent dueto
background radiation, Gol is the open-loop voltagegain, Tk is the
absolute temperature, Cpd is capacitanceof the photodetector per
unit area, η is the FET channelnoise factor, gm is the FET
transconductance, and I2 andI3 are the noise-bandwidth factors with
values 0.562and 0.0868 respectively. Shot noise and thermal
noiseare dependent on the area of the photodetector, anddepending
on factors such as room temperature, ambientlight etc. either of
them can dominate the overall noise[23] observed by the VLC
receiver.
3.1.5 ShadowingThe receiver of a visible light communication
link can beshadowed by different objects or humans in the
indoorenvironment. For example, if a receiver photodiode
ispositioned on a desk, it is possible that movement ofthe nearby
chair can result in shadowing of the receiver.Similarly, if a human
passes by frequently between the
-
11
transmitter and the receiver, the link performance isaffected by
the frequent shadowing. Authors in [32]studied such case of human
mobility using simula-tions and suggested that in multiple
spatially sepa-rated LED sources should be used in order to
mitigatethe frequent disconnections due to human shadowing.Apart
from this preliminary work, shadowing in indoorVLC networks is not
studied in literature. Given thatvisible light exhibits
significantly different propagationcharacteristics compared to RF
(such as no penetrationthrough walls etc.), it is crucial to
characterize and modelvisible light shadowing in indoor
environment. Thisunderstanding can also provide insights on
deploymentaspects of indoor VLC networks and how they shouldbe
different than current deployment of LEDs which areprimarily used
for illumination purposes.
3.2 Modulation Methods
With the understanding of path-loss, noise and SNR,we now
discuss various modulation methods used inVLC. The most striking
difference between VLC andRF is that in VLC, the data can not be
encoded inphase or amplitude of the light signal [10]. This
meansthat phase and amplitude modulation techniques cannot be
applied in VLC and the information has to beencoded in the varying
intensity of the emitting lightwave. The demodulation depends on
direct detectionat the receiver. These set of modulation techniques
arereferred as IM/DD (Intensity Modulated/Direct Detec-tion)
modulations. In this section, we will discuss theIM/DD modulation
techniques used for visible lightcommunication.
Different from other types of communications, anymodulation
scheme for VLC should not only achievehigher data rate but should
also meet the requirementsof perceived light to humans. These
requirements aboutperceived light can be characterized by following
twoproperties -
(1) Dimming: It was suggested in [17] that differentlevels of
illuminance is required when performing differ-ent types of
activities. As an example, an illuminance inthe range of 30-100 lux
is often enough for simple visualtasks performed in most public
places. On the otherhand, office or residential applications
require higherlevel of illuminance in the range of 300-1000 lux.
Withthe advancements in LED driver circuits, it has becomepossible
to dim an LED to an arbitrary level dependingon the application
requirement to save energy.
If an LED can be dimmed to an arbitrary level, it isalso
necessary to understand its impact on the humanperceived light. It
was first shown in [33] that the relationbetween the measured light
and the perceived light isnon-linear. This property is shown in
Fig. 12. In otherwords, a human eye adapts to lower illumination
byenlarging the pupil to allow more light to enter theeye. The
perceived light can be calculated [33] from the
0
10
20
30
40
50
60
70
80
90
100
0 10 20 30 40 50 60 70 80 90 100
Me
asu
red
Lig
ht
(%)
Perceived Light (%)
Fig. 12: Human eye perceives the actual measured
lightdifferently due to enlargement/contraction of pupil.
measured light as
Perceived light(%) = 100×√
Measured light(%)
100(24)
This means that a lamp that is dimmed 1% of its mea-sured light
is perceived to be 10% dimmed by the humaneye. This is important in
terms of VLC because a usermay choose an arbitrary level of dimming
dependingon the application or desired energy savings, but
thecommunication should not be affected by the dimming.In other
words, the data should be modulated in such away that any desired
level of dimming is supported.
(2) Flicker mitigation: An additional requirement forany VLC
modulation scheme is that it should not resultin human-perceivable
fluctuations in the brightness ofthe light. It was shown in [34]
that flickering can causeserious detrimental physiological changes
in humans.For this reason, it is necessary that changes in the
lightintensity should happen at a rate faster than human eyecan
perceive. IEEE 802.15.7 standard [8] suggests thatflickering (or
change in light intensity) should be fasterthan 200 Hz to avoid any
harmful effects. This meansthat any modulation scheme for VLC
should mitigateflickering while providing higher data rate.
The most common cause of flickering is long runs of 0sor 1s
which can reduce the rate at which light intensitychanges and cause
the flickering effect. Run LengthLimited (RLL) codes are used to
mitigate long runs of0s or 1s. RLL codes ensure that the output
symbols havebalanced repetition of 0s and 1s. Examples of
commonlyused RLL codes include Manchester, 4B6B and 8B10Bcoding. In
Manchester coding, a “0” is replaced witha “down” transition (“10”)
and “1” is replaced withan “up” transition (“01”). 4B6B coding maps
a 4 bitssymbol to a 6 bits symbol that has balanced
repetition.Similarly, 8B10B maps a 8 bits symbol to 10 bits
symbol.The number of additional bits added is the highest inthe
Manchester coding making it a suitable choice forlow data rate
services that require better balancing. Onthe other hand, 8B10B
reduces the number of additionalbits added (high data rate),
however, it performs poorly
-
12
in terms of the DC balancing.We next discuss four types of
modulation schemes
used in VLC (1) On-Off Keying, (2) Pulse modulation,(3)
Orthogonal Frequency Division Modulation (OFDM)and (4) Color Shift
Modulation (CSK). We describe eachof them along with a discussion
on how they providethe dimming support.
3.2.1 On-Off Keying (OOK)In OOK, the data bits 1 and 0 are
transmitted by turningthe LED on and off respectively. In the OFF
state, theLED is not completely turned off but rather the
lightintensity is reduced. The advantages of OOK includeits
simplicity and ease of implementation. OOK-likemodulation is widely
used in wireline communication.
Most of the early work on using OOK modulation forVLC utilize
while LED. As we discussed in Section 2,such LED produces white
light by combining the blueemitter with yellow phosphor. The major
limitation ofthe white LED is its limited bandwidth (few
megahertz[35]) due to slow time response of the yellow phos-phor.
It was first proposed by [36] to use NRZ (Non-Return-to-Zero) OOK
with the white LED and a datarate of 10 Mbps was demonstrated over
a VLC link.To further improve the performance, [35] used a
bluefilter to remove the slow-responding yellow component,resulting
in a datarate of 40 Mbps. Similarly, [37] and [38]proposed to
combine the blue-filtering with analogueequalization at the
receiver to achieve data rates of100 Mbps and 125 Mbps
respectively. Authors in [39]showed that the performance can be
further improvedby using an avalanche photodiode as the receiver
insteadof the P-I-N photodiode. The achievable data rate
withavalanche photodiode and NRZ-OOK was shown tobe 230 Mbps. Newly
available white LEDs combinethe RGB frequencies to produce the
white light. Theadvantage of such LEDs is that they do not have
theslow-responding yellow phosphor layer. However, suchRGB white
LEDs require three separate driver circuitsto realize the white
light. A different approach waspresented in [40] where RGB white
LED was used butonly the red LED is modulated for data
transmissionwhile the other two are provided constant current
forillumination. The proposed system can achieve a datarate of 477
Mbps with simple NRZ-OOK modulation anda P-I-N photodiode
receiver.
There are two ways proposed in the Standard IEEE802.15.7 [8] to
provide the dimming support when usingOOK as the modulation
scheme:
1) Redefine ON and OFF levels: To achieve the desiredlevel of
dimming, the ON and the OFF levels can beassigned different light
intensities. The advantageof this scheme is that required level of
dimming canbe obtained without any additional
communicationoverhead. It can retain the data rate achievable
byNRZ-OOK modulation, however, the communica-tion range decreases
at lower dimming levels. Onemajor disadvantage is that using lower
intensities
as ON/OFF levels causes the LEDs to be operatedat lower driving
currents which in turn has shownto incur changes in color rendering
(change inemitted color of LEDs) [41].
2) Compensation periods: In this solution, the ON andthe OFF
levels of the modulation remain the samebut additional compensation
periods are addedwhen the LED source is fully turned on (calledON
periods) or off (OFF periods). The durationof the compensation
periods is determined basedon the desired level of dimming.
Specifically, ONperiods are added if the desired level of dimmingis
more than 50% and OFF periods are added if thedesired level of
dimming is less than 50%. Authorsin [42] proposed a way to
calculate the percentagetime of active data transmission (γ) within
thetransmission interval T to obtain a dimming levelof D as
γ =
{(2− 2D)× 100 : D > 0.5
2D × 100 : D ≤ 0.5(25)
When the desired dimming level is D with OOK,the maximum
communication efficiency ED can becalculated [42] using information
theoretic entropyas
ED = −D log2D − (1−D) log2(1−D) (26)
This means that communication efficiency is atriangular function
of the dimming level with max-imum efficiency at dimming level of
50%. Theefficiency drops linearly when dimming level de-creases to
0% or increases to 100%. The dimmingsupport using compensation
periods reduces thedata rate, however, since the modulated
ON/OFFsignals have unchanged intensity, the communi-cation range
remains unchanged. To address theproblem of lower data rate with
compensationperiods, [43] proposed to use inverse source codingto
maintain the high data rate while achieving thedesired level of
dimming.
3.2.2 Pulse Modulation MethodsAlthough OOK provides various
advantages such assimplicity and ease of implementation, a major
limita-tion is its lower data rates especially when
supportingdifferent dimming levels. This has motivated the designof
alternative modulation schemes based on pulse widthand position
which are described next.
Pulse Width Modulation (PWM): An efficient way toachieving
modulation and dimming is through the usePWM. In PWM, the widths of
the pulses are adjustedbased on the desired level of dimming while
the pulsesthemselves carry the modulated signal in the form of
asquare wave. The modulated signal is transmitted dur-ing the
pulse, and the LED operates at the full brightnessduring the pulse.
The data rate of the modulated signalshould be adjusted based on
the dimming requirement.
-
13
Mapping bits to QAM symbols
DMT modulation
PWM
Bitstream
LED
x(t)
p(t)
y(t)=x(t)p(t)
50% dimming with PWM
TPWM
TON
t
y(t)=x(t)p(t)p(t)
DMT+PWM signal
t
Fig. 13: Transmitter block diagram of DMT transmitterwith
dimming control (top); An example of how 50%
PWM-controlled dimming signal can be combined witha DMT signal
as proposed in [44] (bottom); Figures
reproduced from [44]
Authors in [45] showed that any dimming level from0% to 100% can
be obtained with high PWM frequency.One benefit of PWM is that it
achieves the dimmingwithout changing the intensity level of pulses,
hence itdoes not incur the color shift (like OOK with
redefinedON/OFF levels) in the LED. The limitation of PWMis its
limited data rate (4.8 kbps in [45]). To overcomethis limitation,
[44] proposed to combine PWM withDiscrete Multitone (DMT) for joint
dimming control andcommunication. The approach decouples the
dimmingbased on PWM and communication based on DMT onthe
transmitter side. As shown in Fig. 13, the bitstreamis divided and
mapped to symbols using QuadratureAmplitude Modulation (QAM). These
QAM symbolsare transmitted on different DMT subcarriers that
arespaced by 1/T in frequency where T is the durationof one symbol.
The DMT signal x(t) is combined withPWM square wave signal p(t)
where the duty cycle isdependent on desired level of dimming. The
resultantsignal y(t) = x(t)p(t) is shown in Fig. 13. It was
alsoshown that dimming constraint limits the achievablethroughput
due to high Bit Error Rate (BER). Authorsin [46] also used QAM on
DMT subcarriers to achieve alink rate of 513 Mbps, however, it does
not address theissue of LED dimming.
Pulse Position Modulation (PPM): Another pulsemodulation method
in visible light communication isbased on the pulse position. In
PPM, the symbol du-ration is divided into t slots of equal
duration, anda pulse is transmitted in one of the t slots. The
po-sition of the pulse identifies the transmitted symbol.Due to its
simplicity, many early designs [47], [48] ofoptical wireless
systems adapted PPM for modulation.In some of the early works of
using PPM for infraredcommunication, authors in [49] proposed the
use of rateadaptive transmission scheme where repetition coding
isapplied to gracefully reduce the throughput in presence
1
0 1
0 1
S1 S2 S3 S4
S1 S2 S3
PWM
PPM
VPPM
OPPM
MPPM . . .
0
Fig. 14: Schematic diagram showing difference betweenPulse Width
Modulation (PWM), Pulse Position
Modulation (PPM), Variable Pulse Position Modulation(VPPM),
Overlapping Pulse Position Modulation
(VPPM) and Multipulse Pulse Position Modulation(MPPM); Sn refers
to nth symbol.
of poor channel conditions. Authors in [50] designeda
rate-variable punctured convolutional coded PPM forinfrared
communication. Such a scheme adapts the mod-ulation order of PPM
and the code rate of puncturedconvolutional codes based on the
channel conditions.For even worse channel conditions, [51] proposed
touse rate adaptive PPM transmission with both repeatedand
punctured convolutional codes to achieve higher bitrate.
Due to the limitations of lower spectral efficiency anddata rate
of PPM (only one pulse per symbol duration),other variants of pulse
position-based modulation havebeen proposed over time. A
generalization of PPM isreferred as Overlapping PPM (OPPM) which
allowsmore than one pulse to be transmitted during the
symbolduration [48] and the different pulse symbols can
beoverlapping (see Fig. 14). [52] showed that OPPM cannot only
achieve a higher spectral efficiency comparedto PPM and OOK but a
wide range of dimming levelscan be obtained along with the high
data rate. Anothergeneralization of PPM was proposed by [53] which
isa scheme referred as Multipulse PPM (MPPM). LikeOPPM, it allows
multiple pulses to be transmitted dur-ing the symbol duration,
however, the pulses within asymbol duration do not have to be
continuous (Fig. 14).It was shown in [48] that MPPM can achieve a
higherspectral efficiency compared to OPPM.
Authors in [54] proposed a variation of PPM that com-bines OPPM
and MPPM in a scheme called OverlappingMPPM (OMPPM). In OMPPM, more
than one pulsepositions are allowed for each optical pulse. It
showsthat OMPPM can improve the spectral efficiency ofMPPM without
the expansion of bandwidth in noiselessphoton counting channel.
Further performance analysis
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14
for noisy channels was presented in [55]. It was shown in[56]
that OMPPM with fewer pulse slots and more pulsesper symbol
duration has better cutoff rate performance.Moreover, Trellis-coded
OMPPM was studied in [57],[58] to show its effectiveness in direct
detection channelswith background noise. In another set of
modulationscheme, Differential PPM (DPPM) was proposed in [59].DPPM
is similar to PPM except that the OFF symbolsafter the pulse in a
PPM symbol are deleted and thenext symbol starts right after the
pulse of the previoussymbol. It was shown in [60] that DPPM
requires signif-icantly less average power than PPM for a given
band-width in an optical communication channel. Authors in[61]
proposed Differential Overlapping PPM (DOPPM)where differential
deletion of OFF symbols is appliedto OPPM, and showed that it
achieves better spectralefficiency and cutoff performance than PPM,
DPPM andOPPM.
Authors in [62] proposed EPPM (Expurgated PPM)where symbols in
the MPPM are expurgated to maxi-mize the inter-symbol distance.
EPPM achieves the samespectral efficiency as PPM, however, it can
be used inVLC to provide dimming support as it can achievearbitrary
level of illumination by changing the numberof pulses per symbol
(code-weight) and the length of thesymbol (code-length) [63]. With
many pulses in a sym-bol, EPPM can also mitigate the flickering as
comparedto PPM. MEPPM (Multi-level EPPM) [64] extends theEPPM
design with support to multiple amplitude levelsin order to
increase the constellation size and spectralefficiency. MEPPM can
also support the dimming andprovides flicker-free communication.
IEEE 802.15.7 [8]standard proposes a pulse modulation scheme
calledVariable PPM (VPPM) which is a hybrid of PPM andPWM. In VPPM,
the bits are encoded by choosing dif-ferent position of pulse as in
PPM, however, the width ofthe pulse can also be modified as needed.
VPPM retainsthe simplicity and robustness of PPM while
allowingdifferent dimming levels by altering the pulse width.
3.2.3 Orthogonal Frequency Division Multiplexing(OFDM)One
limitation of previously discussed single-carriermodulation schemes
is that they suffer from high inter-symbol interference due to
non-linear frequency re-sponse of visible light communication
channels. OFDMhas been widely adopted in the RF communicationdue to
its ability to effectively combat the inter-symbolinterference and
multipath fading. Authors of [65] firstproposed the use of OFDM for
visible light communi-cation. In OFDM, the channel is divided into
multipleorthogonal subcarriers and the data is sent in
parallelsub-streams modulated over the subcarriers. OFDM forVLC can
reduce the inter-symbol interference and doesnot require complex
equalizer, however, there are multi-ple challenges in realizing its
implementation. First, theOFDM technique for RF needs to be adapted
for appli-cation in IM/DD systems such as VLC. This is because
OFDM generates complex-valued bipolar signals whichneed to
converted to real-valued signals. This can beachieved by enforcing
Hermitian symmetry constrainton the sub-carriers and then
converting the time-domainsignals to unipolar signals.
Depending on how the bipolar signals are convertedto unipolar,
there are two types of OFDM techniques: (1)Asymmetrically-Clipped
Optical OFDM (ACO-OFDM)and (2) DC-biased Optical OFDM (DCO-OFDM).
InACO-OFDM, only odd subcarriers are modulated [66]which
automatically leads to symmetric time domainsignal. While in
DCO-OFDM [65], [67], [68], all sub-carriers are modulated but a
positive direct current isadded to make the signal unipolar. [69]
presented acomparison of both the OFDM schemes and showedthat LED
clipping distortion is more significant in DCO-OFDM compared to
ACO-OFDM. The biggest challengein OFDM VLC system is the
non-linearity of LED [70]which is that the relationship between the
current andthe emitted light of the LED is non-linear. This
especiallyaffects the OFDM-based VLC systems which have
higherPeak-to-Average Power Ratio (PAPR). The effect of
thisnon-linearity was studied in [71], [72] and a solutionwas
proposed to combat it by operating the LED in asmall range where
the driving current and optical powerare quasi-linear. Apart from
the non-linearity, there isonly a limited support for dimming [73]
in OFDM-basedmodulation schemes. Despite these challenges, OFDMfor
VLC holds great potential with achievable link ratesin the scale of
multiple gbps [74], [75] using only singleLED.
3.2.4 Color Shift Keying (CSK)To overcome the lower data rate
and limited dim-ming support issues of other modulation schemes,
IEEE802.15.7 standard [8] proposed CSK modulation whichis
specifically designed for visible light communication.CSK has
attracted increasing amount of attention fromresearch community in
last couple of years [76]–[81].As we discussed before, generating
white light usingblue LED and yellow phosphorus slows down the
fastswitching ability of LED and hinders high data
ratecommunication. An alternative way to generating whitelight
which is recently becoming more and more popularis to utilize three
separate LEDs - Red, Green and Blue(RGB). This combined source with
RGB LEDs is oftenreferred as TriLED (TLED). CSK modulates the
signalusing the intensity of the three colors in the TLED
source.
CSK modulation relies on the color space chromaticitydiagram as
defined by CIE 1931 [18] (see Fig. 15). Thechromaticity diagram
maps all colors perceivable byhuman eye to two chromaticity
parameters - x and y. Theentire human visible wavelength is divided
into sevenbands as shown in Table 3 and their centers are markedin
Fig. 15. Based on the diagram, the CSK modulation[8], [81] is
performed as follows
1) Determine RGB constellation triangle: The con-stellation
triangle is decided based on the cen-
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15
001
000
010
011
100101110
Constellation triangle
(a)
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8
y
x
4CSK Symbols
(b)
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8
y
x
8CSK Symbols
(c)
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8
y
x
16CSK Symbols
(d)
Fig. 16: (a) RGB constellation triangle (110, 010, 000) (b-d)
Symbols of 4-CSK, 8-CSK and 16-CSK.
001
000
010
011
100101110
Fig. 15: CIE 1931 Chromaticity Diagram; The sevencolor codes
correspond to the centers of seven bands
dividing the visible spectrum as shown in Table 3;reproduced
from [82].
Band (nm) Code Center (nm) (x, y)380-478 000 429 (0.169,
0.007)478-540 001 509 (0.011, 0.733)540-588 010 564 (0.402,
0.597)588-633 011 611 (0.669, 0.331)633-679 100 656 (0.729,
0.271)679-726 101 703 (0.734, 0.265)726-780 110 753 (0.734,
0.265)
TABLE 3: The seven bands used in CSK and their code,center and
chromaticity coordinates.
ter wavelength of the three RGB LEDs used inthe TLED source.
Table 4 shows the valid colorband combinations as proposed by [81]
that canbe chosen as the constellation triangle dependingon the
central wavelength of the RGB LEDs. Forthe purpose of illustration,
let us assume that wechoose the CSK constellation triangle to be
(110,010, 000) as shown in Fig. 16a (example adaptedfrom [81]).
2) Mapping data bits to chromaticity values: De-pending on 4CSK,
8CSK or 16CSK being used,the chromaticity values of symbols can be
derivedfrom the constellation triangle. For our example,Figs. 16b,
16c and 16d show how data bits can
Band i Band j Band k1 110 010 0002 110 001 0003 101 010 0004 101
001 0005 100 010 0006 100 001 0007 011 010 0008 011 001 0009 010
001 000
TABLE 4: Valid color band combinations that can bechosen for
building the constellation triangle for CSK.
be represented using the symbols for 4CSK, 8CSKand 16CSK.
Determining the position of the sym-bols in the constellation
design requires solving anoptimization problem where the distance
betweenthe symbols should be maximized to minimizethe inter-symbol
interference. Note that there is anadditional constraint in the
problem which ensuresthat the symbols should be equally distributed
inthe triangle so that the combined light emittedwhen transmitting
different symbols is perceivedby the human eye to be white light
only. Theoptimization problem has been studied in [76]–[79]as we
discuss next. Once the symbol coordinatesare decided, each symbol
is assigned a bit sequence(e.g. in 4CSK, the 4 symbols are assigned
00, 01, 10and 11 respectively), which is then used to map
theincoming bits to the symbols.
3) Determine the intensities of RGB LEDs: Thesymbols are
transmitted by varying the intensitiesof the RGB LEDs. The
individual intensities ofthe three LEDs (Pi, Pj and Pk) for each
symbol iscalculated by solving the following equations:
xs = Pixi + Pjxj + Pkxk (27)ys = Piyi + Pjyj + Pkyk (28)
Pi + Pj + PK = 1 (29)
where xs and ys are the chromaticity values of thesymbol (Fig.
16), and (xi, yi), (xj , yj) and (xk, yk) arethe chromaticity
values of the central wavelength of theRGB LEDs being used (three
points of the constellationtriangle). The receiver uses the R, G
and B intensities to
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16
decode the transmitted signal.Dimming support in CSK is simply
amplitude dim-
ming where the driving current of the LEDs is variedto change
the brightness of resultant white light. Also,different from OOK
and pulse modulations, flickeringis not a problem with CSK since no
amplitude varia-tion is employed. Due to these advantages,
researchershave recently attempted to improve the CSK scheme ofIEEE
802.15.7 by designing its generalized forms witharbitrary
constellation. Authors in [76] presented a CSKconstellation design
technique based on Billards equiv-alent disk packing algorithm.
Similarly, [77] and [78]developed similar techniques with the use
of differentoptimization algorithms such as interior point
methods.All the constellation design techniques are designed tomeet
the color balance requirement where the TLEDsource is required to
produce any desired color for illu-mination. The use of four LEDs
(blue, cyan, yellow andred) was suggested in [79]. With four LEDs,
it is possibleto achieve a quadrilateral constellation shape that
allowsQAM-like constellation design. The presented system isshown
to be more energy efficient as well as reliable (lessinter-symbol
noise) compared to the conventional CSKwith 3 LEDs.
The RGB tri-LED can also be used to implement Wave-length
Division Multiplexing (WDM) - a multiplexingtechnique commonly used
in fiber optics communica-tion. Authors in [83] proposed modulating
separate datastreams on three colors which together multiplex
towhite light. With the use of DMT, an aggregate data rateof 803
Mbps was shown to be achievable using singleRGB LED in [83].
Authors in [84] proposed the use ofcarrier-less amplitude and phase
modulation on WDMVLC system with RGB LED to achieve a data rate of
3.22Gbps.
IEEE 802.15.7 Physical Layer IEEE 802.15.7 [8] stan-dard has
specified three PHY layers for VLC with atotal of 30 MCS
(Modulation and Coding Scheme) in-dexes. These MCS levels are shown
in Tables 5, 6 and7. Both PHY I and PHY II utilize OOK and VPPMfor
modulation. PHY I utilizes Reed Solomon (RS) andConvolutional Codes
(CC) for Forward Error Correction(FEC), while PHY II and III mostly
reply for RS codesonly for FEC.
As described in [80], “optical clock rate” is an impor-tant
parameter for the performance of the PHY layers.PHY 1 utilizes
lower optical rate of ≤ 400KHz. This isbecause PHY 1 is designed to
be usable in outdoor sce-narios as well where the LED transmitters
are typicallyhigh-power and can switch the intensity at a slower
rate.PHY II is designed to be used indoors where the
opticalswitching rate can be as high as 120 MHz. The opticalrate is
24 MHz for PHY III which is the current feasibleswitching rate for
white TriLED.
Depending on the choice of modulation, RLL code,optical clock
rate, FEC code, the three PHY modes canprovide different data
rates. PHY I can provide data ratesfrom 11.67 Kbps upto 266.6 Kbps.
PHY II can achieve
data rates from 1.25 Mbps upto 96 Mbps. PHY III canyield data
rates starting from 12 Mbps upto 96 Mbps.Further details of
physical layer of IEEE 802.15.7 areprovided in [80].
Table 8 provides a comparison between four majormodulations
schemes proposed for VLC. It can be ob-served that OFDM and CSK are
more suitable for highdata-rate applications in VLC access
networks. As wewill discuss next, OFDM is also more suitable for
VLCMIMO design, however, more research is necessary toensure
dimming support in OFDM. Another advantageof CSK is that it can
provide multi-user access throughwavelength multiplexing as we will
discuss in Section 4.Increasing demand of higher data-rates is
likely to drivefurther research and development of OFDM and CSKfor
VLC-based access networks.
3.3 Multiple Input Multiple Output (MIMO)In order to provide
sufficient illumination, most of theluminaires typically contain
multiple LEDs. These mul-tiple LEDs can be treated as multiple
transmitters thatcan enable visible light MIMO communication. In
RFcommunications, MIMO systems are commonly used(in IEEE 802.11n,
Long-Term Evolution - LTE) to obtainhigher data rates. Similarly,
multiple LEDs can be usedfor higher spectral efficiency in VLC.
Note that there arecertain similarities between the VLC MIMO
systems dis-cussed in this section and screen-camera links
(discussedin Section 6.2) as both of them can use an image sensoras
a MIMO receiver. The difference is that unlike smart-phone screens,
the multiple LED transmitters consideredhere are also used for the
illumination. We will providefurther details of the screen-camera
links in Section 6.2.
MIMO systems in VLC are difficult to realize com-pared to RF
communications. In RF MIMO systems, thethroughput gains are largely
attributed to spatial diver-sity (existence of multiple spatial
paths that are diversein nature). However, such diversity gains are
limitedin VLC MIMO because paths between the transmitterand
receiver are very similar (less diverse) especiallyin indoor
scenarios. This limits the available spatialdiversity of VLC MIMO
systems. The other challenge inVLC MIMO is the design of the
receiver as we discussnext.
3.3.1 MIMO ReceiverAs we discussed in Section 2, there can be
two typesof receivers in VLC MIMO systems - photodiode andimage
sensor. The performance of the system depends onwhether imaging
(image sensor) or non-imaging (photo-diode) receiver is used
[85].
Non-imaging receiver in a MIMO system is a set ofindependent
photodiodes each with its individual con-centrator optics. The
advantage of such a receiver isthat a very high gain can be
achieved due to narrowFOV of each photodiode. The disadvantage,
however, isthat such a receiver requires careful alignment with
the
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17
MCS Modulation RLL code Opticalclock rateFEC Data rate
(kbps)Outer code (RS) Inner code (CC)
0
OOK Manchester 200 KHz
(15,7) 1/4 11.671 (15,11) 1/3 24.442 (15,11) 2/3 48.893 (15,11)
none 73.34 none none 1005
VPPM 4B6B 400 KHz
(15,2) none 35.566 (15,4) none 71.117 (15,7) none 124.48 none
none 266.6
TABLE 5: 802.15.7 PHY I operating mode specifications and
achievable throughput.
MCS Modulation RLL code Opticalclock rate FECData rate(Mbps)
16
VPPM 4B6B
3.75 MHz RS(64,32) 1.2517 RS(160,128) 218
7.5 MHzRS(64,32) 2.5
19 RS(160,128) 420 none 521
OOK 8B10B
15 MHz RS(64,32) 622 RS(160,128) 9.623 30 MHz RS(64,32) 1224
RS(160,128) 19.225 60 MHz RS(64,32) 2426 RS(160,128) 38.427
120 MHzRS(64,32) 48
28 RS(160,128) 76.829 none 96
TABLE 6: 802.15.7 PHY II operating mode specifications and
achievable throughput.
MCS Modulation Optical clock rate FEC Data rate (Mbps)32 4 CSK
12 MHz RS(64,32) 1233 8 CSK RS(64,32) 1834 4 CSK
24 MHz
RS(64,32) 2435 8 CSK RS(64,32) 3636 16 CSK RS(64,32) 4837 8 CSK
none 7238 16 CSK none 96
TABLE 7: 802.15.7 PHY III operating mode specifications and
achievable throughput.
Modulation Data Rate Dimming Support Flickering Issue
CommentsOOK Low to moderate Yes High Low-complexity transceiver
designPPM Moderate Yes Low Maximum spectral efficiency with
MEPPM
OFDM High No Low Complex design due to LED non-linearity, MIMO
supportCSK High Yes Low Requires RGB tri-LED, improved multi-user
access
TABLE 8: Major modulation schemes and their characteristics
transmitters because of the narrow FOV, and the capacitycan
reduce dramatically even with minor misalignment.
Imaging Receiver: Since an image sensor contains aprojection
lens and a large matrix of photodiodes, ithas the potential to
create a high data-rate MIMO link.The projection lens ensures a
large FOV which nearlyeliminates the alignment requirement. The
disadvantageof such as a receiver is that individual photodiodes
havelimited gain and advance image processing is requiredto create
an efficient MIMO channel. Also, the samplingrate of the image
sensor is comparatively lower furtherreducing the achievable
throughput.
The channel models of both imaging and non-imagingreceiver MIMO,
and their relative benefits and limita-tions were presented in
[85]. It was shown in [86] thatan “ideal” MIMO receiver can be a
hybrid of imagingand non-imaging sensors which can achieve high
gains
of LOS paths using narrow FOV like photodiodes andcan be robust
by leveraging non-LOS paths wheneverneeded like an image sensor.
Authors in [87] proposedthe design of a spherically-shaped receiver
that is madeof a large number of photodiodes. Each of the
photodi-ode has a narrow FOV and points in different directionin
the room. The photodiodes pointing to transmitterLED can receive
the signal with high gain while otherphotodiodes pointing to other
directions can establishnon-LOS channels to increase spatial
diversity. However,using such a receiver incurs cost for additional
hardware.Instead, authors in [88] proposed a way to improve
thelower sampling rate of the image sensor. A token-basedpixel
selection method was proposed where instead ofconventional
row-scanning approach, only the pixels ofinterest are selectively
scanned to improve the samplingrate.
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18
3.3.2 VLC MIMO TechniquesThere are three types of VLC MIMO
techniques pro-posed in literature [89].
Repetition Coding (RC): This is the simplest tech-nique where
the same signal is transmitted from all thetransmitters. The
transmitted signal from all LEDs meetconstructively at the
receivers increasing the overall gain.
Spatial Multiplexing (SMP): In SMP, different datais transmitted
from each transmitter to a receiver pho-todiode. With multiple
transmitters and receivers, thistype of MIMO creates multiple
parallel SISO streams.The challenge is that receiver photodiodes
have to beaccurately aligned to the transmitters to avoid any
inter-channel interference. SMP MIMO for optical channelshas been
studied in some of the early works [90]–[92].In [90], [92], authors
proposed optical wireless MIMOcommunication with subcarrier
multiplexing where zeroforcing was utilized to cancel the
interference from othertransmit antennas. It was shown that for the
transmittersemi-angle more than 20o, the transmitter-receiver
sepa-ration should be more than 1.5 meters for lower BER. Theimpact
of optical beat interference on OMIMO schemeof [90] was studied in
[91]. Optical beat interference isthe signal degradation caused by
multiple transmitterstransmitting simultaneously on nearby
wavelengths.
Spatial Modulation (SM): This MIMO technique wasproposed by
[93]–[96] where only one transmitter trans-mits data at any point
of time. The constellation dia-gram is extended to include the
spatial dimension. Eachtransmitter LED is assigned a specific
symbol and whendata bits to be transmitted matches the symbol,
theLED is activated. The receiver estimates which LED wasactivated
based on the received signal, and uses this todecode the
transmitted data. Since the data is encodedin both spatial and
signal domain, SM achieves muchhigher spectral efficiency compared
to other techniques.
A comparison of all the three MIMO techniques wereprovided in
[89]. It was shown that RC is less restrictivein terms of its
requirement for transmitter-receiver align-ment but provides only a
limited spectral efficiency. SMP,on the other hand, requires more
careful alignment oftransmitter-receiver but also provides higher
data ratescompared to RC. SM achieves the best of both worldsby
being robust to correlated channels and providinghigher spectral
efficiency. Also, it was shown in [97]that imaging receivers can
obtain much higher SNRwhen using SM or SMP technique compared to
the non-imaging receivers.
Due to its advantages over other MIMO techniques,SM has been
studied further in recent years. It wasshown in [98], [99] that
power imbalance between thetransmitter LEDs can improve the
performance of spatialmodulation especially when optical paths
between thetransmitter and receiver are highly correlated.
Authorsin [100] studied the performance of spatial modulationusing
an implementation of 4 × 4 MIMO system andshowed that the challenge
in achieving higher through-put with SM is to maintain symbol
separation in the
constellation from the receiver’s perspective.
Researchersinvestigated the performance of spatial modulation
in[101] when only partial channel state information (CSI)is
available and concluded that highly accurate CSIestimation is
necessary to realize the full potential of SM.The use of
generalized spatial modulation was proposedin [102], [103]. Such
modulation extends the originalscheme by allowing more than one
transmitter to beactive during the a symbol duration. It was shown
thatdue to additional flexibility of activating multiple LEDs,the
generalized scheme can achieve higher spectral effi-ciency compared
to the conventional scheme, however,at the cost of additional
complexity in constellationdesign.
Optical MIMO for non-LOS diffuse links has not re-ceived much
attention. Authors in [104] showed howbackward spatial filter can
be used for optical wirelessMIMO in diffuse channels (no precise
alignment oftransmitter and receiver). With user movements,
suchdiffuse channel are more likely in practical scenarios
andoptimizing MIMO performance for such channels shouldbe
investigated further.
3.3.3 Optical Beamforming
Beamforming allows multiple transmitters to concen-trate their
signal in a specific direction based on thereceiver location. This
type of transmit beamforming iswell studied in RF communication and
also utilized byrecent WLAN standards such as IEEE 802.11ac.
Similarto RF beamforming, emitting light from multiple LEDscan be
focused towards the receiver to create opticalbeamforming.
Recently, it was shown in [105] how lightemitted from a single LED
can be focused in a specifictarget direction using Spatial Light
Modulator (SLM).SLM is an additional device that is required to
modu-late the phase or amplitude of the visible light signal.It was
shown that significant SNR improvements canbe achieved by using the
optical beamforming withany modulation technique. Authors in [106]
derivedthe transmit beamforming vectors when multiple LEDsare used
to perform the optical beamforming. Opticalbeamforming can improve
the performance of a visiblelight communication link significantly,
however, thereis only a limited amount of research done
towardsthis. Performing optical beamforming while meeting
theillumination constraints is an important direction forresearch
in VLC MIMO systems.
4 LINK LAYER
When there exists multiple transmitter LEDs and re-ceiver
devices connected to them, it is essential to controlthe medium
access, device association and device mobil-ity. In this section,
we provide an overview of differenttechniques proposed in
literature to manage link layerservices.
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19
Peer-to-peer Star Broadcast
LED Photodiode
Fig. 17: VLC link layer topologies; reproduced from [8]
4.1 Medium Access Control (MAC)The application scenarios of VLC
can be used to identifythe link layer topologies that need to be
supported by theMAC protocols. IEEE 802.15.8 [8] proposes three
typesof link layer topologies for VLC as shown in Fig. 17 -
1) Peer-to-peer: The peer-to-peer topology involvesone device
acting as a coordinator (or master) forthe link between two
devices. Both devices cancommunicate with each other since the
client hasan uplink to the master. This topology is typicallymore
suitable for high-speed Near-Field Commu-nication (NFC).
2) Star: In a start topology, there can be many clientdevices
connected to a master device which acts asthe coordinator. A
typical use case of this topologyis VLC wireless access networks.
The MAC designis especially challenging in the star topology dueto
many bi-directional links in the same collisiondomain.
3) Broadcast: Different from the star topology, theclient
devices in a broadcast topology can onlyreceive data from the
master LED transmitter with-out forming any uplink. Such topology
can be usedfor broadcasting information via LEDs throughoutthe
network. Since there is no explicit associationneeded, the
broadcast topology simplifies the MACdesign.
Three types of multiple access control (MAC) schemesare proposed
for VLC - Carrier Sense Multiple Ac-cess (CSMA), Orthogonal
Frequency Division MultipleAccess (OFDMA) and Code Division
Multiple Access(CDMA).
CSMA: There are two types of random channel accessmechanisms
proposed by IEEE 802.15.7 standard. In thefirst type, the beacons
from the coordinator are disabled.Such beacon-disabled random
access uses an unslottedrandom channel access with CSMA. Here, if a
devicewishes to transmit, it first waits for a random
back-offperiod and then senses the channel to be busy or not,before
transmitting. If the channel is found to be busy,the device waits
for another random period before tryingto access the channel again.
In the second type wherethe beacons are enabled, the time is
divided into beaconintervals. A superframe within the beacon
interval con-tains Contention Access Periods (CAP) and
ContentionFree Periods (CFP) as shown in Fig. 18(a). If a devi