pcm

Transmission Units

Line Characteristics

Distortion, Cross Talk, Impedance Matching in Telecom

Network PCM Principles

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TRANSMISSION UNITS Introduction The study of transmission units has a unique importance for communication engineer who has to maintain and install telecommunication equipments achieving the standards set up by international consultation committees. In order to control the quality of wanted signal in the presence of many undesired signals, we should be able to specify the amount of wanted and unwanted signals at a point in the telecommunications network. The components used in the telecommunication circuit either give loss or gain to the signals they handle. There are certain specific operating conditions to be satisfied for various components without which the optimum performance cannot be obtained from these components. For this, it is essential to define conditions that control those operating conditions. This can be done only if the conditions are specified in terms of certain units of the quantity the components are to handle. Transmission Impairments

With analog transmission systems using copper cable there are three major categories of impairments. They are attenuation, noise, and distortion.

1. Attenuation: There are two commonly used processes to compensate (overcome) for attenuation or loss:

(a) Repeaters are the most commonly used devices to compensate for "Loss." However, repeaters amplify the noise along with the signal resulting in a poor signal to noise ratio.

(b) Signal to Noise Ratio: The ratio of the average signal power (strength) to the average noise power (strength) at any point in a transmission path.

2. Noise: Any random disturbance or unwanted signal on a transmission facility that obscures the original signal. Noise is generally caused by the environment in which the system is operating.

3. Distortion: Inaccurate reproduction of a signal caused by changes in the signal's waveform, either amplitude or frequency, to compensate for distortion equalizers may be used. One type of equalizer used in the analog environment is the load coil. Load coils are used to flatten the frequency response.

Note: Generally the higher the frequency the greater the distortion. That is, the higher voice frequencies attenuate at a higher rate than the lower voice frequencies.

Noise and distortion on a carrier facility can be separated into two types:

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(a) Predictable impairments that are almost always present on our facilities.

(b) Unpredictable impairments those are transient in nature and difficult to overcome. The Decibel And Neper Historically speaking ‘attenuation’ was first of all defined in terms of the attenuation produced by a standard reference cable known as “mile of standard cable”. It consists of 88 ohms series impedance and 0.54 µF as shunt impedance. The fundamental objection to this unit was the fact that the attenuation of the standard cable varied with frequency. With the introduction of systems operating over different frequency ranges, it became necessary to define a unit which was independent of frequency .The unit which represents the useful and convenient concepts in connection with the transmission of signals over telephone lines has been named and defined as “Bel”(which comes from the name Alexander Graham Bell -the inventor of Telephone). In practice ,however , a smaller and more convenient unit called decibel (abbreviated as dB) is used. Decibel (dB) One tenth of the common logarithm of the ratio of relative powers, equal to 0.1 B (bel). The decibel is the conventional relative power ratio, rather than the bel, for expressing relative powers because the decibel is smaller and therefore more convenient than the bel. The ratio in dB is given by

X = log P2/P1 B i.e. = 10 log P2/P1 dB

where P 1 and P 2 are the actual powers. Power ratios may be expressed in terms of voltage and impedance, E and Z, or current and impedance, I and Z. Thus dB is also given by;

X = 20 log V2/ V1 dB. (when Z 1 = Z 2 ) Note: The dB is used rather than arithmetic ratios or percentages because when circuits are connected in tandem, expressions of power level, in dB, may be arithmetically added and subtracted. For example, in an optical link if a known amount of optical power, in dBm, is launched into a fiber, and the losses, in dB, of each component (e.g., connectors, splices, and lengths of fiber) are known, the overall link loss may be quickly calculated with simple addition and subtraction. Example 1 Let us look at the following network: The input is 1W and its output 2W, therefore,

Gain = 10 log (output)/(input) dB. = 10 log 2/1 dB= 10 (0.3010) dB=3.101 dB = 3dB approximately

Example 2 Let us look at another network:

Net Work 1 W 2 W

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Loss = 10 log Input/Output =10 log 1000/1 dB =10 log 103 dB

=30 log 10 dB = 30 dB

Thus a network with an input of 5 W and output of 10 W is said to have Gain = 10 log 10/5 dB

= 10 log 2 dB =3.103 dB = 3 dB.

Let us remember that doubling the power means a 3 dB gain; likewise halving the power means a 3dB loss. Example 3 Consider a network with a 13 dB gain:

0.1W ?

Gain = 10 log P2/P1 dB = 10 log P2/0.1 dB =13db i.e., log P2/0.1 = 1.3 or P2/0.1 = antilog 1.3 or P2 = 0.1 antilog 1.3 P2 = 2W

Example 4 Consider the following network

1W

What is the power output of this network? To do this without pencil and paper, we would proceed as follows: Suppose the network attenuated the signal by 30 dB. Then the output would be 1/1000 of the input or 1mW. Now 27 dB loss is 3dB less than 30 dB. Thus the output would be twice 1m W i.e., 2mW. (Because the loss is less by 3 dB, the corresponding output will be more i.e. double but not half) It is quite simple. Thus, if we have multiples of 10 or 3 up or 3 down from these multiples, we can work it out in our mind without pencil and paper. Example 5

Network 13 db gain

Net Work 1000 W 1 W

Network 27 dB loss ?W

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Let us take the next example. 10W

We know that the 3 dB gain represents approximately 2 times power gain. So 6 dB gain means 4 times the gain. Therefore, the output = 10x4 = 40 (Likewise a 6 dB loss would represent approx. 1/4 of the input power as output i.e. 10/4 = 2.5W)

Example 6 Consider a network of 33 dB gain with an input level of 0.15W. What would be the output? 30 dB represents multiplying the input power by 1000 and 3 additional dBs double it. In this case the input power is multiplied by 2000. Thus the answer is 0.15 x2000 = 300 W. Now work out the output in the same case if

i. the gain was 36 dB ii. the loss was 33 dB

The transmission unit normally used is the decibel. The other unit, however, is also used in some East European countries.

NEPER The natural logarithm of the ratio of two voltages (or currents) expresses the loss or gain in Nepers, N

i.e. X= loge V1/V2 (N)

when the loss (gain) is X Neper, V1 and V2 are voltages, then

ex = V1/V2

Example The loss of a transmission system is 1N when 2.72 V input voltage produces 1 V output voltage.

Comparing powers, X= 1/2 loge P1/P2 (N) or e2x = P1/P2 Other transmission units 1 deciNeper (dN) = 0.1 N

1 Centi Neper (cN) = 0.01N 1 MilliNeper (mN) = 0.001 N

Basic derived decibel units DBm

Network 6 db gain 3 W

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Till now decibel has referred to ratios or relative units. We cannot say that the output of an amplifier is 33 dB. We can say that an amplifier has a gain of 33 dB or that a certain attenuator has a 6 dB loss. These figures or units don't give any idea whatsoever of absolute level. Whereas, several derived decibels units do.

Perhaps the dBm is the most common of these. By definition dBm is a power level related to 1 mw. The most important relationship to remember is:

0 dBm = 1mW.

The dBm formula may then be written as:

Power (in dBm) = 10 log Power (mW)/(1mW)

Example An amplifier has an output of 20 W; what is its output in dBm?

Power (dBm) = 10 log 20 W/1 mW = 10 log 20x103 mW/1mW = +43 dBm.

(The plus sign indicates that the quantity is above the level of reference, 0 dBm.) dBmO Decibel referred to 1 mw at zero (0) Transmission level point. dBmO is a measure of power with reference to Zero dBm at the Reference Transmission Level Point (RTLP).

The RTLP is also known as Zero Transmission Level Point (0TLP). Powers measured at any transmission level point can be expressed in dBmO, by correcting the power measured for the difference in level between the point of measurement and the RTLP.

For example, a level of +25 dBm measured at a +17 dB transmission level point is equivalent to 8 dBmO. Conversely a level of +8 dBmO is also equivalent to +3 dBm measured at a -5 dB transmission level point. A level expressed in dBmO is, therefore, only a relative level.

Conversion from Neper to decibel and Vice Versa We know that decibel is fundamentally a unit of power ratio but it can be used to express current ratios when the resistive components of the impedance, through which the current flows, are equal.

The Neper, on the other hand, is fundamentally a unit of current ratio but it can also be used to express power ratios when the resistive components, of the impedance, through which the current flows, are equal.

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Because of its derivation from the exponential e, the Neper is the most convenient unit for expressing attenuation in theoretical works. The decibel, on the other hand, being defined in terms of logarithms to base 10, is a more convenient unit in practical calculations using the decimal system.

The conditions under which the two units may be used can be summarised in the following equations, the notation of which is indicated in Fig below.

Where Z1 and Z2 are characteristic impedances R1 and R2 are pure resistances G1 and G2 are leakances β1 and β 2 are phase angles X1 and X2 are reactance.

Attenuation in dB = 8.686 x attenuation in Nepers

(provided that R1 = R2) Attenuation in Nepers = 0.1151 x attenuation in dB

(provided that R1 =R2)

Other Units In Analogue Transmission system, the quality of communication is mainly assessed by the value of Signal to noise ratio. Signal-to-Noise Ratio It is popularly known as SNR. SNR is the ratio of signal power to the noise power at any point in a circuit. This ratio is usually expressed in Decibels (dB). For satisfactory operation of a channel the value of SNR should be sufficiently high i.e., the signal power should be sufficiently higher than the noise power. SNR at any point in a circuit is given as SNR = S/N = Signal Power / Noise Power

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Both powers are expressed in watts. Expressing dBs: SNR = 10 log10 (S/N) dB. Example: Signal voltage Vs = 0.923 µV; Noise voltage Vn = 0.267 µV, then calculate the signal-to-noise ratio. S/N = Vs2 / Vn2 = 0.923/0.267)2 = 11.95 In decibels, S/N = 10 log10 (11.95) = 10.77 dB. In Digital Transmission system, the quality of communication is mainly assessed by two factors.

1. BER (Bit Error Ratio) 2. Jitter

These two factors can be taken as Quality Factors as they are used for judging the quality of Digital Transmission. Bit Errors In the digital transmission, the bits transmitted at the transmitting end (1 or 0 ) are not always detected as 1 or 0 at the receiving end. When the transmitted bit 1 or 0 is not identified as 1 or 0 at the receiver, the bit is counted as an error bit. For assessing the real error performance, the bit error ratio (BER) is to be calculated instead of actual error bits. Bit Error Rate (BER) The BER is the measure or error bits with respect to the total number of bits transmitted in a given time. The total number of bits transmitted can be known from the bit rate of the digital signal. The bit rate is the number of bits transmitted in one second and is specified for each transmission system. Hence, the total number of bits transmitted in a given time can be counted. In the measurement of BER, generally the measuring instrument measures the number of bits transmitted in a given time.

The time setting can be from a few seconds to a few hours, depending on the feasibility. The standards are set by ITU (International Telecommunication Union). The time set for the measurement of BER, is called gating time. Larger the gating time better is the assessment of BER. But for the measurement of BER, the Digital Equipment has to be taken off-line.

Digital communication can just run with one error bit in one thousand bits received. For more than one error bit, in one thousand bits received, communication gets affected.

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For good quality communication, the requirement is, not more than one error bit in one million bits. JITTER Abrupt and unwanted variations of one or more signal characteristics, such as the interval between successive pulses, the amplitude of successive cycles, or the frequency or phase of successive cycles. Jitter must be specified in qualitative terms (e.g., amplitude, phase, pulse width or pulse position) and in quantitative terms (e.g., average, RMS, or peak-to-peak). The low-frequency cut-off for jitter is usually specified at 1 Hz. Contrast with drift, wander.

Short term variations of the significant instances of a digital signal from their reference position in time.( Short term frequency equal to or greater than 10 Hz.). Long term variations of significant instances of a digital signal from their ideal positions in time, are called wander. (Long-term variations – frequency less than 10 Hz).

Drift: A comparatively long-term change in an attribute or value of a system or equipment operational parameter. The drift should be characterized, such as "diurnal frequency drift" and "output level drift." Drift is usually undesirable and unidirectional, but may be bi-directional, cyclic, or of such long-term duration and low excursion rate as to be negligible. Wander: Relative to Jitter and swim, long-term random variations of the significant instants of a digital signal from their ideal positions. Wander variations are those that occur over a period greater than 1 s (second). Jitter, swim, wander, and drift have increasing periods of variation in that order. Swim: Slow, graceful, undesired movements of display elements, groups, or images about their mean position on a display surface, such as that of a monitor. Swim can be followed by the human eye, whereas Jitter usually appears as a blur. Jitter, like BER, is another transmission impairment. It is not very significant in the case of voice signal transmission but it has a great impact in the transmission of data signals, especially with high-speed digital transmission. The present bit rates are as high as 565 Mb/s and (140 x 16) Mb/s. Today Jitter is considered as a performance parameter of any digital transmission system.

For example, Jitter due to unwanted phase change is called Phase Jitter. The amount of change of phase, converted into time, is generally expressed in milli-seconds or nano-seconds.

BER and Jitter are the unwanted by products of any transmission system and they get associated with the transmission path and affect the quality of transmission. Bit Errors beyond a limit, affect the communication and Jitter in the digital transmission system, is a source of generation of errors.

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Digital Transmission Analyser (DTA) is used for the measurement of both BER and Jitter. Digital Transmission - Performance Criteria ( General) 1 in 106 (1.OE – 6) : Better 1 in 105 (1.OE – 5) : Good

1 in 104 (1.OE – 4) : Reasonably good 1 in 103 (1.OE – 3) : Just Acceptable More than 1 in 103 : Unacceptable Bit errors greatly affect data service. For data channels 1 in 109 (1.OE – 9) is normally realizable.

Quality Parameters To pin point the exact number of seconds or minutes, in which the bit errors take place and up to what extent, the quality parameters are defined.

The quality parameters are:

1. Error Seconds (ES) 2. Severely Error Seconds (SES) 3. Non Severely Error Seconds (NSES) 4. Degraded Minutes (DM).

Error Seconds (ES): Number of one-second intervals with one or more errors. Severely Error Seconds (SES): Number of one-second intervals with an error rate, worse than 1.OE-3

Non-Severely Error Seconds (NSES): Number of one-second intervals with an error rate, better than or equal to 1.OE-3. Degraded Minutes (DM): Number of one-second intervals with a bit error rates worse than 1.OE-6. Available and non-available time A period of available time begins with a period of ten consecutive seconds each of which has a BER better than 1.0E-3. These 10 seconds are considered to be available time. A period of unavailable time begins when the bit error rate in each second is worse than 1.0E-3 for a period of 10 consecutive seconds. These 10 consecutive seconds are considered to be unavailable time.

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LINE CHARACTERISTICS

Introduction Line transmission is the theory of the propagation of electric waves along transmission lines. These transmission lines are assumed to consist of a pair of wires that are uniform throughout their whole length. When this uniformity holds good, it is immaterial, for the general theory, whether the two wires are air-spaced on telegraph poles, are two conductors in our underground cable, or form a pair in a field quad cable. The infinite line The propagation of elastic waves along any uniform and symmetrical transmission line may be deduced in terms of the results for a hypothetical line of infinite length having electrical constants per unit length identical to those of the line under consideration. For this reason, the propagation of electric waves along an infinite line will be considered first.

When an alternating voltage is applied to the sending end of an infinite length of line, a finite current will flow due to the capacitance and the leakage conductance between the two wires constituting the line. The ratio of the voltage applied, to the current flowing, will give the input impedance. This input impedance is known as the “ characteristic impedance” of the line, and is denoted by ZO.

The characteristic impedance of any line is defined as the impedance looking into an infinite length of the line.

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Short line terminated in Zo

Consider an infinite line having input terminals 1 and 2 as in fig 2(a). The impedance looking in at terminals 1 and 2 will, by definition, be Zo. Suppose that a short section AB at the near end of the line is now removed [fig 2(b)], so that the line now starts at terminals 3 and 4. The impedance looking in at terminals 3 and 4 will still be ZO, since the removal of the short section does not affect the infinite nature of the line. This means that the short section AB, from the electrical point of view, was originally terminated in impedance ZO at B. If the short section AB is now terminated in actual impedance ZO, the current and voltage at all points along its length will be exactly the same as if it were terminated in an infinite length of line. Therefore, it follows that any short line terminated in ZO behaves electrically, at all points along its length, as if it were an infinite line. Determination of ZO for a short line A short line may be considered as a complex network and can be represented as by a T section. If the short line is terminated in ZO, it will behave as an infinite line, and have input impedance ZO. Since the T section represents the line, it also must have input impedance ZO. Let the equivalent T section have series arms Z1/2, Z1/2 and shunt arm Z2 as in fig.3.

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Hence for a short line, ZO can be determined if Z1 and Z2 can be found. This

will require two equations, which may be obtained by measuring the impedance using two different terminating impedances. For convenience these termination will be taken as zero and infinity. Let the input impedance with an infinite- impedance termination i.e. open- circuit, be Zoc. As in fig. 4(a)

ZOC = Z1 + Z2 ..................... (1)

2 Let the input impedance with a zero impedance termination i.e., short- circuit, be Zsc. As in fig 4(b).

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.

Therefore, the characteristic impedance of a line is the geometric mean of the

open and closed circuit impedance. Note: The following measurements have been made on a line at 1600 Hz.

Zoc = 900Ω∠-30° Zsc = 400Ω∠-10° Zo = √Zoc x Zsc

= √900Ω∠-30° x 400Ω∠-10° = 600 Ω∠-20°

Currents and Voltages along an infinite line Consider a current IS applied to the sending end A of an infinite line as in fig 5(a). At the point B, at a distance of one mile down the line, let the current be I1.

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Fig 5. Currents along an infinite line.

Due to the loss introduced by the line, the current I1 will be less than IS and also a phase-shift will be introduced. Therefore the ratio IS / I1 will be a vector quantity. A convenient way of representing a vector quantity is in the form eγ, where γ is a complex quantity. Hence, let IS / I1= eγ.

Where γ is known as the "propagation constant” per mile of the line.

Attenuation and phase constants The propagation constant, γ is a complex quantity. Let it be equal to α+ jβ.

IS /I1= e γ = eα+ jβ.

= eα∠β

IS /I1 = eα and angle of Is /I1 = ∠β

Hence α = loge IS /I1

α is known as the attenuation constant per mile of the line and is measured in Nepers. β is known as the phase constant or wavelength constant per mile of the line, and is measured in radians per mile. If the length of the lime is n miles, then

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IS/In = enχ = enα+njβ = enα∠nβ

The attenuation of such a line is nα Nepers and the phase shift is nβ radians. Line constants

A practical line has a characteristic impedance, a propagation constant γ an attenuation constant α , and a phase constant β . These are known as “ secondary line constants.” Although they are referred to as constants, in general, all will vary if the frequency is changed. The “ primary line constants’ (which, for the purpose of transmission theory, are assumed to be independent of frequency) are R, G, L and C where

R is the resistance per mile of the line, measured in ohms. G is the leakance per mile of the line, measured in mhos. L is the inductance per mile of the line, measured in henries C is the capacitance per mile of the line, measured in farads.

They are measured considering both conductors, i.e. per mile loop. These primary constants may be obtained by measurements on a sample of the line. Relationship between primary and secondary line constants

Consider a short length of line, l mile long. This short section will have a resistance Rl, a leakance Gl, an inductance Ll, and a capacitance Cl. Its characteristic impedance will be Z0, the same as that of the complete line. Its propagation constant will be γl, where γ is the propagation constant per mile of the complete line. This short section of line may be represented as

If the length of the section is very small, Z1 will be approximately equal to the series impedance of the section. i.e. Rl + jwLl; and Z2 will be approximately equal to the shunt impedance of the section, i.e. 1/Gl+jwCl.

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The accuracy of the statement increases as l decreases, and in order to obtain an accurate answer it will be assumed that the section is so small that l tends to zero. Determination Z0 in terms of primary constants It has been shown that for a T section

when ‘w’ is very small, Z0 → √R/G when ‘w’ is very large, Z0 → √L/C

Since R/G, in all cases, is greater than L/C, the variation of Z0 with frequency, expected for a practical line, will be as in fig 6.

Fig. 6 Characteristic impedance of a line. Determination of γ in terms of primary constants

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γ = √(R+jwL)(G+jwC)

1α and β are given by the following equations respectively.

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DISTORTION IN TELECOMMUNICATION CIRCUITS

Introduction

A signal is said to have suffered distortion if, after passing through a network, (passive* or active **) is not an exact replica of the original signal in respect of its amplitude wave shape. * A passive network does not require power supply. It may consist of resistors, coils and condensers either singly or in different combinations e.g. attenuators and filters are passive networks. ** An active network is one that invariably requires power supply. It may consist of an electron tube, a transistor or an IC chip in combination with other components like resistors, coils, and condensers e.g. an amplifier or an oscillator. Signal distortion is of two kinds.

a) Linear distortion b) Non linear distortion

Linear distortion takes place in passive networks. Different types of linear distortion are;

1. Attenuation distortion 2. Phase distortion

Imperfect attenuation, frequency response and phase-frequency characteristic of a network cause attenuation and phase distortions respectively. Non-linear distortion takes place in active networks only and is caused by their excessive loading. Different types of non-linear distortion are;

a. Amplitude distortion b. Frequency distortion c. Inter-modulation distortion

Attenuation distortion The term attenuation distortion is employed to the case of a transmission system where there is variation of gain or loss with frequency. It is assessed with the system operated under steady- state condition by applying a series of sinusoidal wave- forms at different frequencies. Fig.1 shows the amplitude- frequency characteristics of an open wire line. Curve A depicts an ideal open wire line with no attenuation distortion. Curve B pertains to the practical one.

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As is clear from the figure, higher frequencies are attenuated more than the lower ones. An ideal band-pass filter should give same loss to all the frequencies of the pass-band but in actual practice it is not so. The above figure shows a typical attenuation distortion curve for a voice channel. Curve A shows the attenuation-frequency response of an ideal band pass filter and curve B shows the attenuation distortion in the case of a practical band pass filter. As such the network is designed in such a manner that attenuation distortion caused by it remains within permissible limits. However, in the case of open wire carrier lines, equalizers are used to bring amplitude distortion within limits.

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Phase distortion (Envelope delay distortion)

Phase distortion takes place when the time of propagation through a transmission system varies with frequency. Owing to the different relative phase relationships than existing, the output waveform may appear to be quite different from the input waveform, even though the same frequencies are available in the same relative amplitude. Non-linear distortion

"Non linear distortion" is the general name given to a certain type of distortion that occurs when the transmission properties of a system are dependent on the instantaneous magnitude of the applied signal. It is further sub-divided as under:

a) Amplitude distortion. b) Harmonic distortion. c) Inter-modulation distortion.

Amplitude distortion It is defined as the variation of gain or loss of a system with the amplitude of the input. It is measured with the system operated under steady- state conditions with an input of sinusoidal waveform. Harmonic distortion It is due to the production of harmonics in the output when a sinusoidal input of specified amplitude is applied. It is expressed as the ratio of the RMS voltage of all the harmonics in the output, to the total RMS voltage at the output. Inter-modulation distortion It is due to the production of combination frequencies in the output when two or more sinusoidal voltages of specified amplitude are applied at the input. For two parent frequencies p and q, the output may contain frequencies such as (p± q), (1p± q), (p± 2q) etc. in addition to the frequencies p and q.

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CROSS-TALK IN TRANSMISSION MEDIA

Introduction Any disturbing signal produced by transfer of unwanted power from one transmission path (called disturbing circuit) to another transmission path (called disturbed circuit) is known as cross talk. Cross talk may be produced by

• Galvanic, capacitive or inductive couplings between transmission media (Linear cross-talk) e.g. between pairs of a VF (voice frequency) cable system.

• Poor control of frequency response i.e. defective filters or poor filter design is the cause.

• Non-linear performance in analogue (FDM) multiplex systems. A signal transmitted on one circuit or channel of a transmission system (multi-channel) creates an undesired effect in another circuit or channel (non-linear cross talk)

Types of cross talk Broadly speaking, cross talk is of six types.

1. Near-end cross- talk (NEXT). 2. Far-end cross talk (FEXT). 3. Intelligible cross-talk 4. Unintelligible cross-talk 5. Interaction cross-talk 6. Reflected cross-talk

Near-end cross talk (NEXT)

Near-end cross talk occurs if the cross talk power in the disturbed channel propagates in the direction opposite to the propagation of useful power in the disturbing channel. Refer to figure for illustration of near-end cross talk. The terminals of the disturbed channel, at which the near-end cross talk is present, and the energized terminal of the disturbing channel, are usually near each other. The near-end cross talk is much stronger than far-end cross talk because the magnetic (or galvanic) and electrostatic inductions are additive in the case of near-end cross talk and the inducing current in the disturbing circuit is much stronger.

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Far-end cross-talk (FEXT) It occurs if the cross talk power in the disturbed channel propagates in the direction of the propagation of the useful power in the disturbing channel. Refer to Fig. 2 for illustration of far-end cross talk. The terminals of the disturbed channel, at which the far-end cross talk is present, and the energized terminals of the disturbing channel, are usually remote from each other. Far-end cross talk is less effective in impairment of the original signal in the disturbed circuit because the magnetic and electrostatic inductions are subtractive. Also the inducing current in the disturbing circuit gets very much attenuated after it has travelled to the far end.

Intelligible cross talk The cross talk is intelligible when the whole or an important part, of the speech on the disturbing circuit is intelligible on the disturbed circuit. Between circuits transmitting the same frequency band or working without frequency translation (audio-frequency) only intelligible cross talk can arise. As the secrecy of the conversation is affected by intelligible cross talk, steps should be taken to see that intelligibility of sentence articulation of the cross talk should be less than 10%.

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Unintelligible cross talk (also called noise) The cross talk is unintelligible when the disturbing circuit gives rise only to noise in the disturbed circuit. It decreases the intelligibility but does not endanger the secrecy of conversation. Unintelligible cross talk occurs

• Between carrier channels having different frequency allocations. • Between carrier channels having virtual carrier frequencies essentially

differing from each other and • In consequence of non-linear distortion.

Interaction cross talk (Indirect cross talk) Interaction cross talk conveyed by a third circuit from the disturbing circuit to the disturbed circuit, where it causes far end cross talk (fig.3). This type of cross talk is also called double near-end cross talk. It occurs mainly in two-wire carrier systems fitted with intermediate repeaters.

Fig3. Interaction Cross Talk (Double Near End Cross Talk)

Reflected cross-talk Indirect cross talk caused by reflection due to mismatch of the circuit is called reflected cross talk.

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I - Disturbing Circuit. II – Disturbed Circuit. (a) Reflected near-end cross talk causes far- end cross talk. (b) Near-end cross talk caused by reflected wave at far-end causes FEXT. Causes of cross-talk

Cross talk is mainly caused by two types of induction viz., Magnetic and

Electrostatic. Magnetic induction It is well known that a change in magnetic lines of forces is associated with the flow of electric currents. The magnetic lines of forces due to currents flowing through circuit A will also embrace the wires of circuit B. As the current in circuit A alternates, the magnetic field also alternates, and according to Faraday' law it induces e.m.fs in the wires of circuit B Electrostatic induction Electrostatic induction occurs due to the capacitance between four wires of the two circuits that are built side by side. Practically it is noted that the current due to magnetic induction flows in one direction in the entire circuit, whereas that due to the electric induction flows through the two sections in opposite directions Methods for reducing cross talk

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There are a number of methods for eliminating or at least substantially reducing cross talk in open-wire lines. Since the cross talk reduction in open wire lines depends upon three factors viz. Wire configuration, transposition and resistance unbalance. One possible method is to arrange the wires in such a configuration that the effect of the electric and magnetic fields of one pair will be the same on both wires of the disturbed pair, thus leaving no residual difference to cause currents in the disturbed circuit.

Another method to reduce the cross-talk is to reduce the separation between the wires of either or both disturbing and the disturbed pairs and, if possible, to increase the separation between the pairs themselves.

The most commonly used method is the use of " transpositions".

Transposition means interchanging the position of the two wires forming the pair at regular intervals on the pole route, right through the length of the pair. The transposition is by far the most effective and practical method of reducing cross talk.

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IMPEDANCE MATCHING IN TELECOM NETWORK

Introduction In telecom networks, such as attenuators, equalizers and amplifiers etc., impedance matching is of paramount importance to affect the transfer of maximum energy from one telecom network into another. Correct impedance matching also reduces the impairment to the transmission of telecom signals. For example in the case of impedance mismatch between the two telecom networks, say a cable pair and an amplifier input terminals, reflection of the signal takes place and the reflected signal travels back to the talking subscriber. It amounts to echo and is extremely annoying to the talker and can interfere with his normal process of speech. Impedance matching Since it can be designed to have any desired impedance values looking in either direction, a simple resistance pad can be used to match any two resistive-impedance. It, however introduces high attenuation loss. Impedance may also be matched by a T or X pads made up entirely of inductors and capacitors. Though such a pad would introduce relatively little loss, its effectiveness as an impedance matching device would be limited to the frequency for which the reactance values have been determined. Repeating coils and transformers come under this category. The reading of power level at a point in a circuit can be obtained in two ways.

(a) Level or through measurement, (b) Transmission terminating or loss measurement.

Level or through measurement A level measurement is obtained by tapping a high-impedance voltmeter across the circuit, as in Fig 1. The high impedance of the meter is essential to ensure that it will not disturb the circuit under test. (Ex. a 5000 ohms meter will introduce a shunt loss of 0.5 dB). If the impedance of the circuit under test is 600 ohms, the meter will give correct reading in dBs. Any variation in circuit impedance from 600 ohms will destroy the accuracy of the measurement. In case, however the impedance is known, a correction factor may be applied.

28

In transmission circuits, sometimes the impedance encountered is 75 ohms or 150 ohms instead of the standard 600 ohms impedance. Correction factors for that impedance are calculated below:

E = voltage at a point in a circuit. 150 = impedance at the said point. Power indicated on dB meter = E2 / 600 Actual Power = E2 / 150 Error = 10 log10 150/600 = 6 dB

i.e. the meter will read 6 dB. Which implies that 6 dB is to be added to the meter reading to arrive at the correct power level. Similarly, the correction factor for level measurement at a point of 75 ohms impedance is -9 dB. Transmission, terminating or loss measurement

A transmission measurement is made by terminating the circuit in a 600 ohms resistance and measuring the voltage across it using the meter. Refer fig.

29

Many decibel meters having both facilities, a high impedance meter being used, the 600 ohms resistance for TRANS measurement being brought into circuit by operation of a switch and failure to cut off the 600 ohms when making a LEVEL measurement will give a reading that is 3.52 dB low. The meter shows E/3 where as voltage reading should be E / 2.

Discrepancy of reading = 20 log 2 / 3 = - 3. 52 dB.

Reflection loss The phenomenon of reflection is very common in our every day life. When we look into a mirror or hear an echo, we know that these are due to reflection of light and sound wave respectively. From these, it can be deduced that any wave suffers reflection whenever there is an abrupt change of medium through which the wave is propagating. In the case when electromagnetic energy being propagated over a transmission line, the wave motion is guided, between the two wires constituting the line and is called a “ guided “ wave or a “ travelling “ wave. The transmission line may further be connected to equipment or to another transmission line having different electrical characteristics, thus causing change of medium and hence reflection of energy takes place. The electrical characteristic that causes reflection is the impedance of medium. Any variation in impedance will cause reflection. Similarly impedance mismatch in networks (active or passive) causes reflection. One direct consequence of reflection is that the amount of power transferred to the load differs from that when matching conditions exist. All theoretical treatments of networks and transmission lines are based on the condition of perfect matching, which can only be approximated in practical applications. Hence the difference between the matched and non-matched condition is expressed as a “ Reflection loss “ Return loss Return loss is defined as,

20 log 1 / reflection co-efficient

in which, Reflection co-efficient = reflected signal / incident signal at the point of impedance discontinuity or impedance mismatch

30

PCM PRINCIPLES 1.0 INTRODUCTION

1.1 A long distance or local telephone conversation between two persons

could be provided by using a pair of open wire lines or underground

cable as early as early as mid of 19th century. However, due to fast

industrial development and an increased telephone awareness,

demand for trunk and local traffic went on increasing at a rapid rate. To

cater to the increased demand of traffic between two stations or

between two subscribers at the same station we resorted to the use of

an increased number of pairs on either the open wire alignment, or in

underground cable. This could solve the problem for some time only as

there is a limit to the number of open wire pairs that can be installed on

one alignment due to headway consideration and maintenance

problems. Similarly increasing the number of open wire pairs that can

be installed on one alignment due to headway consideration and

maintenance problems. Similarly increasing the number of pairs to the

underground cable is uneconomical and leads to maintenance

problems.

1.2 It, therefore, became imperative to think of new technical innovations

which could exploit the available bandwidth of transmission media such

as open wire lines or underground cables to provide more number of

circuits on one pair. The technique used to provide a number of circuits

using a single transmission link is called Multiplexing.

2.0 MULTIPLEXING TECHNIQUES

2.1 There are basically two types of multiplexing techniques

i. Frequency Division Multiplexing (FDM)

ii Time Division Multiplexing (TDM)

31

2.2 Frequency Division Multiplexing Techniques (FDM) The FDM techniques is the process of translating individual speech

circuits (300-3400 Hz) into pre-assigned frequency slots within the

bandwidth of the transmission medium. The frequency translation is

done by amplitude modulation of the audio frequency with an

appropriate carrier frequency. At the output of the modulator a filter

network is connected to select either a lower or an upper side band.

Since the intelligence is carried in either side band, single side band

suppressed carrier mode of AM is used. This results in substantial

saving of bandwidth mid also permits the use of low power amplifiers.

Please refer Fig. 1.

FDM techniques usually find their application in analogue transmission systems.

An analogue transmission system is one which is used for transmitting

continuously varying signals.

2.3 Time Division Multiplexing 2.3.1 Basically, time division multiplexing involves nothing more than sharing

a transmission medium by a number of circuits in time domain by

establishing a sequence of time slots during which individual channels

(circuits) can be transmitted. Thus the entire bandwidth is periodically

32

available to each channel. Normally all time slots1 are equal in length. Each

channel is assigned a time slot with a specific common repetition period called

a frame interval. This is illustrated in Fig. 2.

2.3.2 Each channel is sampled at a specified rate and transmitted for a fixed

duration. All channels are sampled one by, the cycle is repeated again

and again. The channels are connected to individual gates which are

opened one by one in a fixed sequence. At the receiving end also

similar gates are opened in unision with the gates at the transmitting

end.

2.3.3 The signal received at the receiving end will be in the form of discrete

samples and these are combined to reproduce the original signal. Thus, at

a given instant of time, onty one channel is transmitted through the medium, and

by sequential sampling a number of channels can be staggered in time as

opposed to transmitting all the channel at the same time as in EDM

systems. This staggering of channels in time sequence for transmission

over a common medium is called Time Division Multiplexing (TDM).

33

3.0 PULSE CODE MODULATION SYSTEM

3.1 It was only in 1938, Mr. A.M. Reaves (USA) developed a Pulse

Code Modulation (PCM) system to transmit the spoken word in

digital form. Since then digital speech transmission has become an

alternative to the analogue systems.

3.2 PCM systems use TDM technique to provide a number of circuits

on the same transmission medium viz open wire or underground cable

pair or a channel provided by carrier, coaxial, microwave or satellite

system.

3.3 Basic Requirements For PCM System

To develop a PCM signal from several analogue signals, the

following processing steps are required

34

• Filtering

• Sampling

• Quantisation

• Encoding

• Line Coding

4.0 FILTERING

4.1 Filters are used to limit the speech signal to the frequency band 300-

3400 Hz.

5.0 SAMPLING

5.1 It is the most basic requirement for TDM. Suppose we have an

analogue signal Fig. 3 (b), which is applied across a resistor R through a

switch S as shown in Fig. 3 (a) . Whenever switch S is closed, an

output appears across R. The rate at which S is closed is called the

sampling frequency because during the make periods of S, the

samples of the analogue modulating signal appear across R. Fig. 3(d) is

a stream of samples of the input signal which appear across R. The

amplitude of the sample is depend upon the amplitude of the input

signal at the instant of sampling. The duration of these sampled pulses

is equal to the duration for which the switch S is closed. Minimum

number of samples are to be sent for any band limited signal to get a

good approximation of the original analogue signal and the same is

defined by the sampling Theorem.

35

FIG. 3 : SAMPLING PROCESS

5.3 Sampling Theorem

5.3.1 A complex signal such as human speech has a wide range of

frequency components with the amplitude of the signal being different

at different frequencies. To put it in a different way, a complex signal

will have certain amplitudes for all frequency components of which the

signal is made. Let us say that these frequency components occupy a

certain bandwidth B. If a signal does not have any value beyond this

bandwidth B, then it is said to be band limited. The extent of B is

determined by the highest frequency components of the signal.

5.3.2 Sampling Theorem States

"If a band limited signal is sampled at regular intervals of time and at a

rate equal to or more than twice the highest signal frequency in the

band, then the sample contains all the information of the original

signal." Mathematically, if fH is the highest frequency in the signal to be

sampled then the sampling frequency Fs needs to be greater than 2 fH.

i.e. Fs>2fH

5.3.3 Let us say our voice signals are band limited to 4 KHz and let sampling

frequency be 8 KHz.

Time period of sampling Ts = 1 sec 8000

36

or Ts = 125 micro seconds

If we have just one channel, then this can be sampled every 125 microseconds

and the resultant samples will represent the original signal. But, if we are to

sample N channels one by one at the rate specified by the sampling theorem,

then the time available for sampling each channel would be equal to Ts/N

microseconds.

5.3.4 Fig. .4 shows how a number of channels can be sampled and

combined.

The channel gates (a, b ... n) correspond to the switch S in Fig. 3. These

gates are opened by a series of pulses called "Clock pulses". These are called

gates because, when closed these actually connect the channels to the

transmission medium during the clock period and isolate them during the OFF

periods of the clock pulses. The clock pulses are staggered so that only one

pair of gates is open at any given instant and, therefore, only one channel is

connected to the transmission medium. The time intervals during which the

common transmission medium is allocated to a particular channel is called the

Time Slot for that channel. The width of.this time slot will depend, as stated

above, upon the number of channels to be combined and the clock pulse

frequency i.e. the sampling frequency.

37

FIG. 4: SAMPLING & COMBINING CHANNELS

5.3 In a 30 channel PCM system. TS i.e. 125 microseconds are divided into

32 parts. That is 30 time slots are used for 30 speech signals, one time

slot for signalling of all the 30 chls, and one time slot for

synchronization between Transmitter & Receiver.

The time available per channel would be Ts/N = 125/32

= 3.9 microseconds

Thus in a 30 channel PCM system, time slot is 3.9 microseconds and time

period of sampling i.e..the interval between 2 consecutive samples of a channel

is 125 microseconds. This duration i.e. 125 microseconds is called Time

Frame.

5.4 The signals on the common medium (also called the common highway)

of a TDM system will consist of a series of pulses, the amplitudes of

which are proportional to the amplitudes of the individual channels at

their respective sampling instants. This is illustrated in Fig. 5

38

i

FIG 5 : PAM OUTPUT SIGNALS

5.5 The original signal for each channel can be recovered at the receive end by

applying gate pulses at appropriate instants and passing the signals through

low pass filters. (Refer Fig. 6)

Fig. 6 : RECONSTRUCTION OF ORIGINAL SIGNAL

39

6.0 QUANTISATION

6.1 In FDM systems we convey the speech signals in their analogue

electrical form. But in PCM, we convey the speech in discrete form. The

sampler selects a number of points on the analogue speech signal (by

sampling process) and measures their instant values. The output of the

sampler is a PAM signal as shown in Fig. 3; The transmission of PAM

signal will require linear amplifiers at trans and receive ends to recover

distortion less signals. This type of transmission is succeptible to all the

disadvantages of AM signal transmission. Therefore, in PCM systems,

PAM signals are converted into digital form by using Quantization

Principles. The discrete level of each sampled signal is quantified with

reference to a certain specified level on an amplitude scale.

6.2 The process of measuring the numerical values of the samples and

giving them a table value in a suitable scale is called "Quantising". Of

course, the scales and the number of points should be so chosen that

the signal could be effectively reconstructed after demodulation.

6.3 Quantising, in other words, can be defined as a process of breaking

down a continuous amplitude range into a finite number of amplitude

values or steps.

6.4 A sampled signal exists only at discrete times but its amplitude is drawn

from a continuous range of amplitudes of an analogue signal. On this

basis, an infinite number of amplitude values is possible. A suitable

finite number of discrete values can be used to get an. approximation of

the infinite set. The discreate value of a sample is measured by

comparing it with a scale having a finite number of intervals and

identifying the interval in which the sample falls. The finite number of

amplitude intervals is called the "quantizing interval". Thus, quantizing

means to divide the analogue signal's total amplitude range into a

number of quantizing intervals and assigning a level to each intervals.

For example, a 1 volt signal can be divided into 10mV ranges like 10-

20mV, 30-40mV and.so on. The interval 10-20 mV, may be designated

40

as level 1, 20-30 mV as level 2 etc. For the purpose of transmission,

these levels are given a binary code. This is called encoding. In practial

systems-quantizing and encoding are a combined process. For the

sake of understanding, these are treated separately.

6.5 Quantizing Process

6.5.1 Suppose we have a signal as shown in Fig. 7 which is sampled at instants a,

b, c, d and e. For the sake of explanation, let us suppose that the signal has

maximum amplitude of 7 volts.

In order to quantize these five samples taken of the signal, let us say the total

amplitude is divided into eight ranges or intervals as shown in Fig. 7. Sample (a)

lies in the 5th range. Accordingly, the quantizing process will assign a binary

code corresponding to this i.e. 101, Similarly, codes are assigned for other

samples also. Here the quantizing intervals are of the same size. This is

called Linear Quantizing.

FIG. 7 : QUANTIZING-POSITIVE SIGNAL

41

6.5.2 Assigning an interval of 5 for sample 1, 7 for 2 etc. is the quantizing

process. Giving, the assigned levels of samples, the binary code is

called coding of the quantized samples.

6.5.3 Quantizing is done for both positive and negative swings. As shown in

Fig. 6, eight quantizing levels are used for each direction of the

analogue signal. To indicate whether a sample is negative with

reference to zero or is positive with reference zero, an extra digit is

added to the binary code. This extra digit is called the "sign bit". In Fig.

8. positive values have a sign bit of ' 1 ' and negative values have sign

bit of'0'.

42

FIG. 8 : QUANTIZING - SIGNAL WITH + Ve & - Ve VALUES 6.6 Relation between Binary Codes and Number of levels. 6.1 Because the quantized samples are coded in binary form, the quantization

intervals will be in powers of 2. If we have a 4 bit code, then we can have 2" =

16 levels. Practical PCM systems use an eight bit code with the first bit as

sign bit. It means we can have 2" = 256 (128 levels in the positive direction

and 128 levels in the negative direction) intervals for quantizing. 6.7 Quantization Distortion

Practically in quantization we assign lower value of each interval to a sample

falling in any particular interval and this value is given an

Table-1 : Illustration of Quantization Distortion

Analogue Signa

Amplitude Range

Quantizing Interval

(mid value) Quantizing Level Binary Code

0-10 mv 5 mv 0 1000

10-20mv 15mv 1 1001

20-30 mv 25 mv 2 1010

30-40 mv 35 mv 3 1011

40-50 mv 45 mv 4 1100

If a sample has an amplitude of say 23 mv or 28 mv, in either case it

will be assigned \he \eve\ "2". This Is represented in binary code 1010.

When this is decoded at the receiving end, the decoder circuit on

receiving a 1010 code will convert this into an analogue signal of

amplitude 25 mv only. Thus the process' of quantization leads to an

approximation of the input signal with the detected signal having some

deviations in amplitude from the actual values. This deviation between

the amplitude of samples at the transmitter and receiving ends (i.e. the

difference between the actual value & the reconstructed value) gives

rise to quantization distortion.

6.7.2 If V represent the step size and 'e' represents the difference in

amplitude fe' must exists between - V/2 & + V/2) between the actual

43

signal level and its quantized equivalent then it can be proved that

mean square quantizing error is equal to (V2). Thus, we see that the

error depends upon the size of the step. 12

6.7.3 In linear quantization, equal step means equal degree of error for all

input amplitudes. In other words, the signal to noise ratio for weaker

signals will be poorer.

6.7.4 To reduce error, we, therefore, need to reduce step size or in other

words, increase th,e number of steps in the given amplitude range. This

would however, increase the transmission bandwidth because

bandwidth B = fm log L. where L is the number of quantum steps and

fm is the highest signal frequency. But as we knows from speech

statistics that the probability of occurrence of a small amplitude is much

greater than large one, it seems appropriate to provide more quantum

levels (V = low value) in the small amplitude region and only a few (V =

high value) in the region of higher amplitudes. In this case, provided the

total number of specified levels remains unchanged, no increase in

transmission bandwidth will be required. This will also try to bring about

uniformity in signal to noise ratio at all levels of input signal. This type of

quantization is called non-uniform quantization.

6.7.5 In practice, non-uniform quantization is achieved using segmented

quantization (also called companding). This is shown in Fig. 9 (a). In

fact, there are equal number of segments for both positive and

negative excursions. In order to specify the location of a sample value

it is necessary to know the following :

1. The sign of the sample (positive or negative excursion)

2. The segment number

3. The quantum level within the segment

44

As seen in Fig. 9 (b), the first two segment in each polarity are

collinear, (i.e. the slope is the same in the central region) they are

considered as one segment. Thus the total number of segment appear

to be 13. However, for purpose of analysis all the 16 segments will be

taken into account.

7.0 ENCODING

7.1 Conversion of quantised analogue levels to binary signal is called

encoding. To represent 256 steps, 8 level code is required. The eight

bit code is also called an eight bit "word".

The 8 bit word appears in the form

P ABC WXYZ

Polarity bit ‘1’ Segment Code Linear encoding for + ve 'O' for - ve. in the segment

The first bit gives the sign of the voltage to be coded. Next 3 bits gives the

segment number. There are 8 segments for the positive voltages and 8 for

45

negative voltages. Last 4 bits give the position in the segment. Each

segment contains 16 positions.

Referring to Fig. 9(b), voltage Vc will be encoded as 1 1 1 1 0101.

FIG. 9 (b) : ENCODING CURVE WITH COMPRESSION 8 BIT CODE

7.2 The quantization and encoding are done by a circuit called coder. The coder

converts PAM signals (i.e. after sampling) into a 8 bit binary signal. The

coding is done as per Fig. 9 which shows a relationship between voltage V to

be coded and equivalent binary number N. The function N = f(v) is not linear.

The curve has the following characteristics.

It is symmetrical about the origins. Zero level corresponds to zero voltage to

be encoded.

It is logarithmatic function approximated by 13 straight segments numbered

0 to 7 in positive direction and 'O' to 7 in the negative direction. However 4

46

segments 0, 1, 0, 1 lying between levels + vm/64 -vm/64 being colinear are

taken as one segment.

The voltage to be encoded corresponding to 2 ends of successive segments

are in the ratio of 2. That is vm, vm/2, vm/4, vm/8, vm/16, vm/32, vm/64,

vm/128 (vm being the maximum voltage).

There are 128 quantification levels in the positive part of the curve and 128 in

the negative part of the curve.

7.3 In a PCM system the channels are sampled one by one by applying the sampling

pulsqs to the sampling gates. Refer Fig. 10. The gates open only when a pulse

is applied to them and pass the analogue signals through them for the

duration for which the gates remain open. Since only one gate will be activated

at a given instant, a common encoding circuit is used for all channels. Here the

samples are quantized and encoded. The encoded samples of all the channels

and signals etc are combined in the digital combiner and transmitted.

47

7.4 The reverse process is carried out at the receiving end to retreive the original

analogue signals. The digital combiner combines the encoded samples in the

form of "frames". The digital separator decombines the incoming digital

streams into individual frames. These frames are decoded to give the PAM

(Pulse Amplitude Modulated) samples. The samples corresponding to

individual channels are separated by operating the receive sample gates

in the same sequence i.e. in synchronism with the transmit sample gates.

8.0 CONCEPT OF FRAME

48

8.1 In Fig. 10, the sampling pulse has a repetition rate of Ts sees and a

pulse width of "St". When a sampling pulse arrives, the sampling gate

remains opened during the time "St" and remains closed till the next

pulse arrives. It means that a channel is activated for the duration "St".

This duration, which is the width of the sampling puse, is called the

"time slot" for a given channel.

8.2. Since Ts is much larger as compared to St. a number of channels can

be sampled each for a duration of St within the time Ts. With reference

to Fig. 10, the first sample of the first channel is taken by pulse 'a',

encoded and is passed on the combiner. Then the first sample of the

second channel is taken by pulse 'b' which is also encoded and passed

on to the combiner, Likewise the remaining channels are also sampled

sequentially and are encoded before being fed to the combiner. After

the first sample of the Nth channel is taken and processed, the second

sample of the first channel is taken, this process is repeated for all

channels. One full set of samples for all channel taken within the

duration Ts is called a "frame". Thus the set of all first samples of all

channels is one frame; the set of all second samples is another frame

and so on.

8.3 As already said in para 5.3.5, Ts in a 30 channel PCM system is 125

microseconds and the signalling information of all the channels is

transmitted through a separate time slot. To maintain synchronization

between transmit and receive ends, the synchronization data is

transmitted through another time slot. Thus for a 30 chl PCM system,

we have 32 time slots.

Thus the time available per channel would be 3.9 microsecs.

Thus for a 30 chl PCM system,

Frame = 125 microseconds

Time slot per chl = 3.9 microseconds.

8.4 Structure of Frame

8.4.1 A frame of 125 microseconds duration has 32 time slots. These slots

are numbered Ts 0 to Ts 31.

49

Information for providing synchronization between trans and receive

ends is passed through a separate time slot. Usually the slot Ts 0

caries the synchronizsation signals. This slot is also called Frame

alignment word (FAW).

The signalling informatiori is transmitted through time slot Ts 16.

Ts 1 to Ts 15 are utilized for voltage signal of channels 1 to 15

respectively.

Ts 17 to Ts 31 are utilized for voltage signal of channels 16 to 30

respectively.

9.0 SYNCHRONIZATION

9.1 The output of a PCM terminal will be a continuous stream of bits. At

the receiving end, the receiver has to receive the incoming stream of

bits and discriminate between frames and separate channels from

these. That is, the receiver has to recognise the start of each frame

correctly. This operation is called frame alignment or

Synchronization and is achieved by inserting a fixed digital pattern

called a "Frame Alignment Word (FAW)" into the transmitted bit

stream at regular intervals. The receiver looks for FAW and once it

is detected, it knows that in next time slot, information for channel

one will be there and so on.

9.2 The digits or bits of FAW occupy seven out of eight bits of Ts 0 in

the following pattern.

Bit position of Ts 0 B1 B2 B3 B4 B5 B6 B7 B8

FAW digit value X 0 0 1 1 0 1 1

9.3 The bit position B1 can be either ' 1 ' or '0'. However, when the

PCM system is to be linked to an international network, the B1

position is fixed at '1 ' .

The FAW is transmitted in the Ts O of every alternate frame.

Frame which do not contain the FAW, are used for

transmitting supervisory and alarm signals.

50

To distinguish the Ts 0 of frame carrying supervisory/alarm signals

from those carrying the FAW, the B2 bit position of the former are

fixed at T. The FAW and alarm signals are transmitted alternatively

as shown in Table - 2.

TABLE-2

Frame Remark

Numbers B1 B2 B3 B4 B5 B6 B7 B8

FO X 0 0 1 1 0 1 1 FAW

F1 X 1 Y Y Y 1 1 1 ALARM

F2 X 0 0 1 1 0 1 1 FAW

F3 etc X 1 Y Y Y 1 1 1 ALARM

In frames 1, 3, 5, etc, the bits B3, B4, B5 denote various types of

alarms. For example, in B3 position, if Y = 1, it indicate Frame

synchronisation alarm. If Y = 1 in B4, it indicates high error density

alarm. When there is no alarm condition, bits B3 B4 B5 are set 0.

An urgent alarm is indicated by transmitting "all ones". The code

word for an urgent alarm would be of the form.

X 111 1111 10.0 SIGNALLING IN PGM SYSTEMS

10.1 In a telephone network,-the signalling information is used for

proper routing of a call between two subscribers, for providing

certain status information like dial tone, busy tone, ring back. NU

tone, metering pulses, trunk offering signal etc. All these functions

are grouped under the general terms "signalling" in PCM

systems. The signaling information can be transmitted in the form

of DC pulses (as in step by step exchange) or multifrequency pulses

(as in cross bar systems) etc.

10.2 The signalling pulses retain their amplitude for a much longer

period than the pulses carrying speech information. It means

that the signalling information is a slow varying signal in time

compared to the speech signal which is fast changing in the time

51

domain. Therefore, a signalling channel can be digitized with less

number of bits than a voice channel.

10.3 In a 30 chl PCM system, time slot Ts 16 in each frame is allocated

for carrying signalling information.

10.4 The time slot 16 of each frame carries the signalling

data corresponding to two VF channels only. Therefore, to cater

for 30 channels, we must transmit 15 frames, each having 125

microseconds duration. For carrying synchronization data for

all frames, one additional frame is used. Thus a group of 16

frames (each of 125 microseconds) is formed to make a

"multiframe". The duration of a multiframe is 2 milliseconds. The

multiframe has 16 major time slots of 125 microseconds duration.

Each of these (slots) frames has 32 time slots carrying, the encoded

samples of all channels plus the signaling and synchronization data.

Each sample has eight bits of duration 0.400 microseconds (3.9/8 =

0.488) each. The relationship between the bit duration frame and

multiframe is illustrated in Fig. 11 (a) & 11 (b).

52

FIG. 11 (B) 2.048 Mb/s PCM MULTIFRAME

10.4 We have 32 time slots in a frame, each slot carries an 8 bit word.

The total number of bits per frame = 32 x 8 = 256

The total number of frames per seconds is 8000

The total number of bits per second are 256 x 8000 = 2048 K/bits.

Thus, a 30 chP PCM system has 2048 K bits.

10.6 Multiframe Structure

10.6.1 In the time slot 16 of FO, the first four bits (positions 1 to 4) contain the

multiframe alignment signal which enables the receiver to identify a multiframe.

The other four bits (no. 5 to 8) are spare. These may be used for carrying

alarm signals.

Time slots 16 of frames F1 to FT5 are used for carrying the signalling

information. Each frame carries signalling, data for two VF channels. For

instance, time slot Ts 16 of frame F1 carries the signal data for VF channel 1 in

the first four bits. The next four bits are used for carrying signalling information

53

for channel 16. Similarly, time slot Ts16 of F2 carries signalling data of chls 2

.and 17.

Thus in multiframe structure, four signalling bits are provided for each VF

channels.

As each multiframe includes 16 frames, each with a sacnqtoq - per

sec.,.the.signalling of each channel will occur at a rate of 500 per sec.