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LC VoltageLC Voltage--Controlled OscillatorsControlled OscillatorsZhangwen Tang
Advisor : Professor Hao Min
[email protected] , http://10.12.240.202
Jun. 4th, 2004
ASIC & System State-Key Laboratory, Fudan University
Copyright © 2001-2004, All Rights Reserved by Zhangwen Tang
Page 2
-2-ASIC & System State-Key Laboratory, Fudan University
http://10.12.240.202, Copyright © 2001-2004, Zhangwen Tang
ContentContentIntroductionFundamentals of LC VCOs On-chip inductorsVaractors and F-V tuning curve Optimization of LC VCOsTechniques of lowering phase noiseDesign examplesConclusion and prospect
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-3-ASIC & System State-Key Laboratory, Fudan University
http://10.12.240.202, Copyright © 2001-2004, Zhangwen Tang
IntroductionIntroduction
PLL
Band LimitedFilter LNA
FirstVCO
Up ConversionMixer Image-
RejectedFilter
AGC
DLIF Architecture of TV tuner for DVB system
SecondVCO
Down ConversionMixer
IF
Off-Chip
Local Oscillators
Novel Architecture for CMOS TV Tuner: DLIFDouble Conversions with Low IF
Discrete TV Tuner Module
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-4-ASIC & System State-Key Laboratory, Fudan University
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PFD LPF
92~158÷ 50÷
PFD LPF
4253~4387÷
12.5MHz
250KHz
LO1
LO2
1150-1975MHz
1063.5-1096.5MHz
LC Tank VCO
LC Tank VCO
Frequency SynthesizersFrequency Synthesizers
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-5-ASIC & System State-Key Laboratory, Fudan University
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2L
C
Vc
Mn1 Mn2
Mp1 Mp2
Mn3
C
High Q, Low Parasitic Resistor Inductors High Q, High Tuning Range MOS Varators
LC VoltageLC Voltage--Controlled OscillatorsControlled Oscillators
CMOS Complementary Cross-coupled –Gm LC VCO
Design issues• Low phase noise• Low power• Wideband tuning range • F-V tuning curve • Quadrature output• etc …
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-6-ASIC & System State-Key Laboratory, Fudan University
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OutlineOutlineIntroductionFundamentals of LC VCOs
Oscillator viewsMathematics of LC VCOsStructures of different LC-VCOs
On-chip inductorsVaractors and F-V tuning curve Optimization of LC VCOsTechniques of lowering phase noiseDesign examplesConclusion and prospect
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-7-ASIC & System State-Key Laboratory, Fudan University
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Oscillator ViewsOscillator Views
( )H s∑inV outV
Two-port view : feedback system One-port view : Negative Resistance
CP RPLPActiveCircuit
RP
( ) ( )( )
=+1
out
in
H sV sV H s
Transfer function
= −active PR R
Active circuit
Barkhausen criterion
( ) ( )ω ω≥ ∠ = °0 01 & 180H j H j ωω
= −1j L
j C
Inductance cancels capacitance
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-8-ASIC & System State-Key Laboratory, Fudan University
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Ring Oscillator and LC OscillatorRing Oscillator and LC Oscillator
+ -
- +
+ -
- +
+ -
- +
A1 A2 An…
Ring oscillator LC-Tank oscillator
Transfer function
( )ωω
= −⎛ ⎞+⎜ ⎟
⎝ ⎠
0
0
1
n
n
AH sj
ω ω°⎛ ⎞
= ⋅ ⎜ ⎟⎝ ⎠
0180tanosc N
°⎛ ⎞⎛ ⎞= + ⎜ ⎟⎜ ⎟⎜ ⎟⎝ ⎠⎝ ⎠
2
01801 tanA
N
Mn1 Mn2
CP
RP
LP
−2
mg
X Y
•Advantage: Large tuning range•Disadvantage: High phase noise
•Advantage: Low phase noise•Disadvantage: Small tuning range
Inductors &MOS Varactor designs
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-9-ASIC & System State-Key Laboratory, Fudan University
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Mathematics of LC Mathematics of LC VCOsVCOs
outω
ctrlV
0ω
1ω
2ω
1V 2V
VKslope
0out V ctrlK Vω ω= + ⋅
( )ex V
ctrl
KsV sφ
=
F-V characteristic function
An ideal integrator in Phase-Locked Loop
Performance parametersCenter frequencyTuning rangeVoltage-controlled gainTuning linearityPhase noiseOscillating amplitudePower dissipation
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-10-ASIC & System State-Key Laboratory, Fudan University
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Narrowband LC Narrowband LC VCOsVCOs
2L
Vc
Mn1 Mn2
Mp1 Mp2
Mn3
CV
LL
Cv
Vc
Mn2Mn1
Itail
Vdd
Vdd
Mn3Itail
Y
Vdd Vdd X Y
Vdd Vdd
VssVss
X
Cfix Cfix Cfix Cfix
Cv CV
NMOS-only –Gm LC VCO Complementary MOS –Gm LC VCO
[Ali Hajimiri, JSSC, May, 1999]
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-11-ASIC & System State-Key Laboratory, Fudan University
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Wideband LC Wideband LC VCOsVCOs
LL
CVCv
Vc
Mn2
Itail
Vdd
Mn3
YX
Cfix
Mn1
C2C4C8C
B0B1B2B3
W/L2W/L4W/L8W/L
8Cd 4Cd2Cd Cd
C 2C 4C 8C
B0 B1 B2 B3
W/L 2W/L 4W/L 8W/L
8Cd4Cd2CdCd
Wideband LC VCO with Switched CapacitorsTradeoffs
MIM capacitorSwitched NMOS transistorQuality of capacitors
[A, Kral, A.A. Abidi, CICC, 1998]
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-12-ASIC & System State-Key Laboratory, Fudan University
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QuadratureQuadrature LC LC VCOsVCOs
Vdd
ItailMp
L1 L2C1 C2
LL
Cv
Vc
Mn2Mn1
X2X1
Cfix Cfix
Cv
LL
Cv
Vc
Mn4Mn3
X4X3
Cfix Cfix
Cv
S1 S2
Quadrature LC VCO with Superharmonic coupling
[S. L. J. Gierkink, JSSC, July, 2003]
Superharmonic couplingat Common-mode, S1 & S2Very simpletwo same LC-VCOsLow phase noiseLow power dissipation
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-13-ASIC & System State-Key Laboratory, Fudan University
http://10.12.240.202, Copyright © 2001-2004, Zhangwen Tang
OutlineOutlineIntroductionFundamentals of LC VCOsOn-chip inductors
Inductor’s ClassModeling of on-chip inductors Optimization of equivalent capacitanceQuality Factor improvement
Varactors and F-V tuning curve Optimization of LC VCOsTechniques of lowering phase noiseDesign examplesConclusion and prospect
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-14-ASIC & System State-Key Laboratory, Fudan University
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Three types of On-chip inductors
Gyrator-based active inductors(a) single-ended,(b) floating configurations
Bondwire inductors
On-chip spiral inductors
InductorInductor’’s Classs Class
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-15-ASIC & System State-Key Laboratory, Fudan University
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Planar Spiral InductorPlanar Spiral Inductor
Number of tuners, nMetal width, wSpacing, sOuter diameter, dout
Inner diameter, din
Fill ratio, Number of sides, N
(a) Square Spiral (b) Hexagonal Spiral
(c) Octagonal Spiral (d) Circular Spiral
( )/( )out in out ind d d dρ= − +
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-16-ASIC & System State-Key Laboratory, Fudan University
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Multilayer Spiral InductorMultilayer Spiral Inductor
5M
4M
3M
5M
4M
5M
4M
3M
5M
3M
Stacked spiral inductor Miniature 3D spiral inductor
Differential multilayer inductor
[A. Zolfaghari, B. Razavi, JSSC, April, 2001] [C.C Tang, S.I. Liu, JSSC, April, 2002]
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-17-ASIC & System State-Key Laboratory, Fudan University
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Modeling of OnModeling of On--chip Inductorschip InductorsCharacteristic of inductance of a typical
integrated inductors with frequencyEM Field Solver
High accuracyVery slowComplex for Spice
Segmental circuit modelsSimpler than EM field solverEasy integration into Spice
Compact, scalable, lumped circuit models
Simple, versatile and robustPhysical intuition
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-18-ASIC & System State-Key Laboratory, Fudan University
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Optimization of Equivalent CapacitanceOptimization of Equivalent CapacitanceWhat is the equivalent capacitance
At resonance frequency, the peak magnetic and electric energies are equal.Given a peak voltage V0, electric energy is
First resonance frequency fSR
The proposed equivalent capacitance modelsElectric energy in interlayer metals, CM-M
Electric energy in single metal to substrate, CM-S
20 2eqC V
( ) 12SR eq eqf L Cπ
−=
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-19-ASIC & System State-Key Laboratory, Fudan University
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Electric Energy in CElectric Energy in CMM--MM and Cand CMM--SS
1 2V V−
i
i
CC
CCCC
C
C
C
1 2V V−nM
1nM −
1V
2V
i
CC
CCCC
CnM
1V
C C
Substrate
2V2V
1V1 2V V V∆ = −
CM-M
CM-S
1
2, ,
1 1
21 2
12
1 ( )2
m m
n n
N N
e C e C m Cm m
M M
E E C V
C wl V V−
= =
−
= =
= −
∑ ∑
2, ,
1 1
21
1
2 21 2 1 2
12
1 ( )2
16
m m
n
n
N N
eC eC m Cm m
NM S
m
N
M S
E E C V
C wl mV VN N
C wl V V VV
= =
−
=
→∞
−
= =
= − ∆
≈ + +
∑ ∑
∑
Electric Energy
Electric Energy
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-20-ASIC & System State-Key Laboratory, Fudan University
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Voltage ProfileVoltage Profile
5M
4M
1C
2C
Substrate
5M
4M
1C
2C
Substrate
0V
0
2V
,1M SC −
1st Turn 2nd Turn 3rd Turn,1M MC −
,2M SC −
,2M MC −
,3M MC −
,3M SC −
Top
Top
Top
Bottom
BottomBottom
0V
0
2V ,1M MC − ,2M MC −
,3M MC −
,3M SC −
,2M SC −
,1M SC −
1st Turn 2nd Turn 3rd Turn
Stacked
Miniature 3D
[A. Zolfaghari, B. Razavi, JSSC, April, 2001]
[C.C Tang, S.I. Liu, JSSC, April, 2002]
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Capacitance CoefficientsCapacitance Coefficients
Stacked
Miniature 3D
1κ 2κ
1 1 2 2eqC C Cκ κ= +
Higher fSR
Small Area
3D or Stacked
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-22-ASIC & System State-Key Laboratory, Fudan University
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Pattern ground shield
Dual reverse-bias PN-junction isolation in deep NwellStop eddy current in skin channel
Quality Factor ImprovementQuality Factor ImprovementMultipath metal
DNW
NWELL
DNW
NWELL NWELL
Psub
PWELL PWELL
Deep Nwell Process
Vdd Gnd
Gnd
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-23-ASIC & System State-Key Laboratory, Fudan University
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OutlineOutlineIntroductionFundamentals of LC VCOsOn-chip inductorsVaractors and F-V tuning curve
Varactors’ classPeriod calculation of LC VCO with step-like varactors
Optimization of LC VCOsTechniques of lowering phase noiseDesign examplesConclusion and prospect
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-24-ASIC & System State-Key Laboratory, Fudan University
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VaractorsVaractors’’ ClassClass
n-well
P+N+ N+
n-well
P+P+ N+
n-well
N+N+
n-well
P+P+ N+
(b) D=S=B MOS(a) p+/n-well Junction
(c) Inversion MOS (d) Accumulation MOS
G
G
G VddVctrl
Vctrl
GVctrl
Vctrl
p-sub p-sub
p-subp-sub
Four Types of Varactors in Silicon CMOS: PN Junction, Standard MOS, Inversion-MOS, Accumulation-MOS
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-25-ASIC & System State-Key Laboratory, Fudan University
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DC Capacitance of MOS DC Capacitance of MOS VaractorsVaractorsD
C C
apac
itanc
e C
ss
DC
Cap
acita
nce
Css
DC
Cap
acita
nce
Css
(a) S=D=B PMOS Varactor (b) Inversion PMOS Varactor (c) Accumulation NMOS Varactor
Vgs@Vctrl=1.65V Vgs@Vctrl=1.65V Vgb@Vctrl=1.65V
2.0p
1.8p
1.6p
1.4p
1.2p
1.0p
0.8p
2.0p
1.8p
1.6p
1.4p
1.2p
1.0p
0.8p
0.6p
2.0p
1.8p
1.6p
1.4p
1.2p
1.0p
0.8p
0 1 2 3 0 1 2 30 1 2 3
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-26-ASIC & System State-Key Laboratory, Fudan University
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StepStep--like like VaractorsVaractors
( ) max effss
min eff
C V VC V
C V V≥⎧
= ⎨ ≤⎩eff G ctrl THV V V V= − −Effective control voltage
( ) ( )= + + − −1 1( ) ( )2 2ss max min max min effC V C C C C sign V V
Small-signal capacitance of step-like varactors
L
Css(V)
Vdd
Vctrl
Cmax
Cmin
VC
1
-1
0
V
Css(V) sign(V)
(a) Serial LC Tank (b) Step-like Varactor (c) Unit Step Function
Vout
Veff
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-27-ASIC & System State-Key Laboratory, Fudan University
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Oscillating Waveforms in LCOscillating Waveforms in LC--TankTank
I-V locus of Step-like varactorOscillating waveforms at different Veff
Two ellipses of different sizes joint with a step transition at Veff
Vdc
Region (2)
Region (4)
Region (3)
Region (1)
Veff=3.5V
Veff=3.0V
Veff=2.0V
Veff=2.5V
T2T1
T
Veff=2.00VVeff=2.25VVeff=2.50VVeff=2.75VVeff=3.00VVeff=3.25VVeff=3.50V
Amin Amax
Imax
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-28-ASIC & System State-Key Laboratory, Fudan University
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Oscillating Period CalculationOscillating Period Calculation
Vvdd<Veff <Vvdd+Amax
Vvdd-Amin<Veff <Vvdd
Veff> Vvdd+Amax
Veff<Vvdd-Amin
Oscillating Period of LC TankEffective Control Voltage, Veff
2max maxT T LCπ= =
2min minT T LCπ= =
( )1
1 12
eff effmax min max min
min max
V VT T T asin T asin T
A Aπ θ⎛ ⎞⎛ ⎞ ⎛ ⎞
= + + −⎜ ⎟⎜ ⎟ ⎜ ⎟⎜ ⎟⎝ ⎠ ⎝ ⎠⎝ ⎠
Ellipse Similar Factor22
1 1 eff eff
min max
V VA A
θ⎛ ⎞⎛ ⎞
= − + ⎜ ⎟⎜ ⎟⎝ ⎠ ⎝ ⎠
( )2
1 12
eff effmax min max min
min max
V VT T T asin T asin TA Aπ θ
⎛ ⎞⎛ ⎞⎛ ⎞= + + − +⎜ ⎟⎜ ⎟⎜ ⎟⎜ ⎟⎝ ⎠ ⎝ ⎠⎝ ⎠
Ellipse Similar Factor2 2
2 1 eff eff
max min
V VA A
θ⎛ ⎞ ⎛ ⎞
= − +⎜ ⎟ ⎜ ⎟⎝ ⎠⎝ ⎠
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Simulation Verification in HSPICESimulation Verification in HSPICE
L=10nH; Vdc=2.5VFmax=1.591GHz; Fmin=0.795GHzCmin=1.0pf; Cmax=4.0pf
Simulation agrees well with the proposed calculation
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-30-ASIC & System State-Key Laboratory, Fudan University
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Comparison with OthersComparison with Others’’ ModelModel
Hegazi’s effective capacitance model
( ) ( )21 1 1
2eff eff eff
eff max min min maxV V VC C C C C asinA A Aπ
⎛ ⎞⎛ ⎞ ⎛ ⎞ ⎛ ⎞⎜ ⎟= + + − + −⎜ ⎟ ⎜ ⎟ ⎜ ⎟⎜ ⎟⎝ ⎠ ⎝ ⎠ ⎝ ⎠⎝ ⎠
Point A
Point B
⋅=
+,2 min max
eff Amin max
F FFF F
⋅=
+, 2 2
2 min maxeff B
min max
F FFF F
The reasons for difference between two method:a) Hegazi’s model is small-signal analysis; b) Neglect 2rd and higher order harmonics;
[E. Hegazi, A.A. Abidi, JSSC, June, 2003]
L=10nH; Vdc=2.5VFmax=1.591GHz; Fmin=0.795GHzCmin=1.0pf; Cmax=4.0pf
Amin=1.0V
Amin=0.5V
Amin=0.25V
feff of Our CaculationA
feff of the effective capacitance model
B
Vdc
≤, ,eff B eff AF F
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-31-ASIC & System State-Key Laboratory, Fudan University
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Validation with OthersValidation with Others’’ LCLC--VCOsVCOs
[Y.B. Choi, 5th ASICON, 2003] [H.L.Lao, 5th ASICON, 2003]
Frequency-Voltage Curves
L=2.825nH; Vdc=1.128VFmax=2.543GHz; Fmin=2.317GHzCmin=1.387pf; Cmax=1.671pfAmin=1.124V; Amax=1.233V
L=2.8nH; Vdc=0.742VFmax=3.984GHz; Fmin=3.537GHzCmin=0.570pf; Cmax=0.723pfAmin=0.749V; Amax=0.844V
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-32-ASIC & System State-Key Laboratory, Fudan University
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OutlineOutlineIntroductionFundamentals of LC VCOsOn-chip inductorsVaractors and F-V tuning curveOptimization of LC VCOs
Low power design and low phase noise Underlying physics of LC oscillatorsOptimization method: Linear and Geometric Programming
Techniques of lowering phase noiseDesign examplesConclusion and prospect
Page 33
-33-ASIC & System State-Key Laboratory, Fudan University
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LowLow--power Designpower Design
L C
RL RC
-R
L
C
R
RLC Tank2 2
2 2peak peakCV LI
=
Energy Conservation Theorem
The loss in RLC tank
2 2 2 20 2 2
0loss peak peak
RP RC V VL
ωω
= =0
1LC
ω =
Low-power designLower serial resistance RIncrease the tank inductanceWork at high frequency
0
0
1 1tank
L LQR CR R Cω
ω= = =
[M. Tiebout, JSSC, Jul. 2001]
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-34-ASIC & System State-Key Laboratory, Fudan University
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LowLow--phasephase--noise Designnoise Design
( )20
2 22 sig
KTLP Q
ωω
ω∆ ∝
∆
Phase noise (SSCR)
Low-phase-noise designLower serial resistance RIncrease the tank inductanceIncrease amplitude voltage
( )3
2 2 2peak
KT RLV L
ωω
∆ ∝∆
0
0
1 1tank
L LQR CR R Cω
ω= = =
tankQ
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-35-ASIC & System State-Key Laboratory, Fudan University
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Underlying Physics of LC OscillatorsUnderlying Physics of LC Oscillators
2L
Vc
Mn1 Mn2
Mp1 Mp2
Mn3
CV
Vdd
Itail
X Y
CV
C Li(t)
Itail
-Itail
i(t)
tankgactiveg- Current limited
Voltage limited
Vdd=2.5V
Vdd=2.0V
Vdd=1.5V
(4 / ) ( )( )
bias tanktank
limit
I g I limitedV
V V limitedπ −⎧
= ⎨ −⎩
tankV
limitV
voltage limited−
Inductance limited−
2L 1L
2A 1A
>2 1tank tank
E E
L
20
( )2( )
tanktank
limit
L limitedE LVV limitedV
ω⎧ −⎪= ⎨ −⎪⎩[A. Hajimiri, JSSC, May 1999]
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NoiseNoise--toto--Carrier Rate, NCRCarrier Rate, NCR
2 / 2 / 2nC v KT⟨ ⟩ =
CR C L R2 2
0nKTv KT LC
ω⟨ ⟩ = =
The equipartition theorem of thermodynamics states that:Any system in equilibrium has a mean energy of KT/2
2
2
1 ( )( )
tankn
tank
E L limitedvV L V limited
−⎧⟨ ⟩∝ ⎨ −⎩
2 2 2 2/ / ( )tank tail tank tail LE I Lg I Lg L limited∝ ≈ −
2 22
2
( )/( )
L tailn
tank
L limitedLg IvV V limitedL
−⎧⟨ ⟩∝ ⎨ −⎩
[D. Ham and A. Hajimiri, JSSC, Jun. 2001]
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Design Insight2LLg
L
tankV
limitedV
,tank minV
NCR
minNCR
optL
feasiblenon feasible−
2LLg
L
tankV
limitedV
,tankminV
NCR
minNCR
optLvoltage linited−inductance limited−
(a) (b)
L L
L L
2LLg increasing with L
Startup conditionMinimum tank amplitudeOptimization at feasible point
descreasing with LOptimization at the verge of inductance-limited and voltage-limited regime
2LLg
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12 initial design variablesMOS transistors
On-chip spiral inductors
MOSCAP varators
Load cap and tail current
loadC loadC
L s pC C C= + L s pC C C= +
pR pR
L LsR sR
vRvRvC vC
NMOS PMOSC C+ NMOS PMOSC C+
( )mn mpg g− + ( )mn mpg g− +
on opg g+ on opg g+
SpiralInductor
MOSVarators
NMOS &PMOS
Transistors
LC VCO TopologyLC VCO Topology
Equivalent oscillator model
, ,v max v minC C
load tailC I
n n p pW L W L
outd w s n
Page 39
-39-ASIC & System State-Key Laboratory, Fudan University
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LC VCO ParametersLC VCO ParameterssC
pR pRpC pC
L sR
vRvC
n-well
N+N+
GVctrl
p-sub
G Vctrl
21 /( )L p sg R R Lω= +
( ) /v v vg C Qω=
2 tank on op v Lg g g g g= + + + 2 active mn mpg g g= +
2tamnkL L= 2 tank PMOS NMOS L v loadC C C C C C= + + + +
, , ,4NMOS gs n db n gd nC C C C= + + , , ,4PMOS gs p db p gd pC C C C= + +
Page 40
-40-ASIC & System State-Key Laboratory, Fudan University
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Design ConstraintsDesign Constraints(1) Power dissipation
(2) Oscillator voltage amplitude
(3) Tuning range
(4) Startup condition
(5) Maximum diameter of spiral inductor
etc. …
tail maxI I≤
,,
2 2tail tail tailtank tank min
tank max on op v L L
I I IV Vg g g g g g
= = ≈ ≥+ + +
, ,2 2
1 1tamnk tank min tank tank max
max min
L C L Cω ω
≤ ≥
( ) ( ), 2max min t min max minrω ω ω ω ω ω− = + =
,active min tank maxg gα≥
maxd d≤
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Phase Noise OptimizationPhase Noise Optimization
2 2
2
2
( )
( )
L
tail
tail
sunpply
L gL limitedI
LL I V limited
V
ω
⎧−⎪
⎪∆ ∝ ⎨⎪ −⎪⎩
In 1/f2 region, Phase noise (SSCR)
2
4
2
2
1( )
( )
s
tail
tail
sunpply
RL limited
L IL
L I V limitedV
ωω
⎧⎛ ⎞⋅ −⎪⎜ ⎟
⎝ ⎠⎪∆ ∝ ⎨⎪ −⎪⎩
( )22/( ) s
L sR
Lg L R LL
ωω
≈ =
Design strategyLower Rs/L of on-chip inductor, or select high QL inductorAt maximum current Imax
At verge of inductance-limited and voltage-limited regime
[D. Ham, and A. Hajimiri, JSSC, 2001] Proposed optimization equation
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0 20 40 60 80 100
4
3
2
1
0
Wn (μm)
Cv(p
F)
T.R.1
T.R.2
Tank amplitude
start-up
Inductance/current-limited
voltage-limited
min 3α < min 3α ≥
A
B
C
regime-divider
0 20 40 60 80 100
4
3
2
1
0
Wn (μm)
Cv(p
F)
T.R.1
T.R.2 Tank amplitude
start-up
A
B
C
Graphical OptimizationGraphical Optimization
Lower Rs/L in on-chip inductor, Decrease or increase Itail
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Geometric ProgrammingWhat?
2 2
2 210 log2
rms n
max
i fLq
ωω
⎛ ⎞Γ ∆∆ = ⋅ ⋅⎜ ⎟⎜ ⎟⋅ ∆⎝ ⎠
00 0
1( ) ( )
2 n nn
c c cos nω τ ω τ θ∞
=
Γ = + +∑ 2 22 2
00
1 ( ) 2n rmsn
c x dxπ
π
∞
=
= Γ = Γ∑ ∫
Object Function: phase noise
Page 44
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OutlineOutlineIntroductionFundamentals of LC VCOsOn-chip inductorsVaractors and F-V tuning curveOptimization of LC VCOsTechniques of lowering phase noise
Limited noise factor for white noiseNoise filtering techniquesInductive control voltage
Design examplesConclusion and prospect
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Limited Noise Factor for White NoiseLimited Noise Factor for White NoiseVdd
Mp1 Mp2
Mn1 Mn2
Mn3
LRs
21pi
22pi
21ni
22ni
2taili
2sRv
C
2sRvRsL
ωω
ω
⎛ ⎞⎜ ⎟ ⎛ ⎞⎛ ⎞∆⎜ ⎟∆ = ⋅ = ⋅ ⎜ ⎟⎜ ⎟⎜ ⎟⎜ ⎟ ∆⎝ ⎠⎝ ⎠⎜ ⎟⎝ ⎠
2, 2
0210 log 10 log
2
n SSBP
sig sig
vR KTfL F
P P Q
Phase noise
γ γγ
+⎛ ⎞= = + = +⎜ ⎟
⎝ ⎠1 1
2n pN
P
RFR
Limited noise factor
C RPL
-RG
2
4nN
VKTR
f=
∆
[F. Herzel and M .Tiebout, TCASII, Jan. 2000]
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Noise Sources of CloseNoise Sources of Close--in Phase Noisein Phase Noise
L ω∆
ω∆
3
1f
2
1f
31f
ω∆
210logs
FkTP
⎛ ⎞⎜ ⎟⎝ ⎠
Flicker noise of tail currentAM-FM modulation
Flicker noise of differential pairsDifferential pairs looks like a “Mixer”.Flicker noise modulates the basebandand 2nd harmonics voltage at the tail.
Varactor nonlinearityAM-FM modulation of common noise, power and substrate noise.
ωω
ωω ω
⎧ ⎫⎡ ⎤ ∆⎛ ⎞⎛ ⎞⎪ ⎪⎢ ⎥∆ = ⋅ ⋅ + ⋅ +⎜ ⎟⎨ ⎬⎜ ⎟ ⎜ ⎟∆ ∆⎢ ⎥⎝ ⎠⎪ ⎪⎝ ⎠⎣ ⎦⎩ ⎭
32
10210 log 1 12
f
s L
FkTLP Q
Leeson’s model
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Noise Filtering Techniques (1)Noise Filtering Techniques (1)
Lower channel length modulationFiltering noise from tail current
[A. Hajimiri, JSSC, May. 1999]
Large capacitor filter at common nodeVdd
Mp1 Mp2
Mn1 Mn2
Mn3
C
L
X Y
S
Ctail
VX VY
VS
VX VY
VS
Without large capacitor
With large capacitor
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Noise Filtering Techniques (2)Noise Filtering Techniques (2)Remove of tail current
Vdd
Mp1 Mp2
Mn1 Mn2
C
L
X Y
S
Vdd
Mp1 Mp2
Mn1 Mn2
Mn3
C
L
X Y
S
Output Voltage
Load Impedance Load Impedance
Output Voltage
(a) Without tail current (b) With tail current
Off Triode Zero
High
Low
High
Roles of the tail current:Supply DC currentBoost high impedance at common-source nodeAvoiding Q-degradation by triode region FETs
[S. Levantino, JSSC, Aug. 2002]
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Noise Filtering Techniques (3)Noise Filtering Techniques (3)LC filter at 2nd harmonic
V d d
M p 1 M p 2
M n 1 M n 2
M n 3
C
L
X Y
S 1
C ta il
V XV Y
V S 1
C 1
C 2
L 1
L 2
S 2
V S 2
N o isea t ω 02
[E. Hegazi, JSSC, Dec. 2001]
L1 & C1, L2 & C2 resonates at 2nd harnonicBoost the impedance at each common-source node, avoiding Q-degradationImprove the oscillating amplitude voltage, and voltage-limited moves into current-limited
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Inductive Control Voltage (Proposed)Inductive Control Voltage (Proposed)
Vctrl
CV CV
Vdd
Mp1 Mp2
Mn1 Mn2
Mn3
L
X Y
S1
Ctail
C1
C2
L1
L2
S2
C3
L3
S3
VX VY
VS1
VS2
VS3Vctrl
L3 & C3 resonates at 2nd harnonicLower even harmonics in oscillating voltageThe oscillating voltage is more symmetric in one period
Page 51
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OutlineOutlineIntroductionFundamentals of LC VCOsOn-chip inductorsVaractors and F-V tuning curveOptimization of LC VCOsTechniques of lowering phase noiseDesign examples
1.08 GHz narrow LC VCO1.0-2.0 GHz wideband LC VCO
Conclusion and prospect
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Example I : 1.08GHz Narrowband LC VCOExample I : 1.08GHz Narrowband LC VCO
Chartered CMOS 0.35µm 2P4M RF/MS process72-side inductor and A-MOS Varactor in Chartered libraryDie Size: 1120µm×820µm
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Simulation and Measurement of FSimulation and Measurement of F--V Curve V Curve
L=5.755nH; V0=2.208VFmax=1.164GHz; Fmin=0.970GHzCmin=3.247pf; Cmax=4.675pfAmin=0.811V; Amax=0.973V
L=5.760nH; V0=2.083VFmax=1.134GHz; Fmin=0.978GHzCmin=3.421pf; Cmax=4.610pfAmin=0.860V; Amax=1.000V
NM5 NM6LC VCOCore
Bias-T
Vdd
Bias-T
Vdd
Spectrum Analyzer50Ωmatching
Bias Current
Test
Simulation Measurement
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Phase Noise (Simulation)Phase Noise (Simulation)
Simulation in Cadence SpectreRF : Bias at 3.1mAPhase Noise < -82.2dBc/Hz@10kHz
-84dBc
-108.6dBc
-129.3dBc
1/f3 Region
1/f2 Region
±8.9%Tuning Range
-82.2dBc/Hz@10kHz-108dBc/Hz@10kHz
-129.3dBc/Hz@10kHz
Phase Noise(Simulation)
945MHz-1137MHzOscillating Frequency
3.1mACurrent
3.3VPower Voltage
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Example II : 1Example II : 1--2 GHz Wideband LC VCO2 GHz Wideband LC VCO
Switched-Capacitor ArrayLC
OscillatorCore
Switched-Current
Array
Encoder
LC oscillator coreSwitched-capacitor arraySwitched-current arrayEncoder
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Differential OnDifferential On--Chip InductorChip Inductor
G GG
GG GS S
S S
OPENTHRU P+
NW
GS
S G
G
G
GL12
>5Single-end Q
5.2nHInductance
1.5 µmSpacing
15 µmWidth
5Turns
16Sides
100µmCore Diameter
De-embeded PAD
Single-end Q
Single-end Inductance
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Simulation and Measurement of FSimulation and Measurement of F--V CurveV Curve
Simulation
Measurement
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Phase Noise (Simulation)Phase Noise (Simulation)
Simulation in Cadence SpectreRF : Bias at 1.15mAPhase Noise < -80dBc/Hz@10kHzDie Size: 1120µm×1200µm
1/f3 Region
1/f2 Region
-79dBc
-104.4dBc
-125.3dBc
±31%Tuning Range
-79dBc/[email protected] /[email protected] /Hz@10kHz
Phase Noise(Simulation)
1041MHz-1968MHzOscillating Frequency
3.5-10mACurrent
3.3VPower Voltage
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PFTN (PFTN (PowerPower--FrequencyFrequency--TuningTuning--NormalizedNormalized))
( )⎡ ⎤⎛ ⎞⎢ ⎥= −⎜ ⎟⎢ ⎥⎝ ⎠⎣ ⎦
2
sup
10log tuneoff
off
fkTPFTN L fP f
[email protected] [20]
[email protected] [19]
[email protected] [18]
[email protected] [17]
[email protected] [16]
[email protected] [15]
[email protected] [14]
[email protected] [13]
[email protected]
[email protected]
OrderPFTN(dB)
Phase noise(dBc/Hz)
Fo(GHz)
ftune(MHz)
Power(mW)
Process(µm)
Reference
Page 60
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ConclusionsConclusionsOn-chip inductors
Equivalent capacitanceDifferential multilayer inductorQuality factor improvement techniques
Varactors and F-V tuning curvePeriod calculation of LC-VCO with step-like varactor
Optimization of LC VCOHigh Q inductor, Lower Rs/L in on-chip inductor
Techniques of lowering phase noiseInductive control voltage
Two design examples
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Prospect(1):Prospect(1): Switched MIMSwitched MIM--Cap Cap Varactor Varactor
C1//C2
C1
VTH VC
Css(V)
C-V Curve
Switched MIM-Cap
Direct Model
Cross Model
C2
G
Vc
C1
M1
C2 C2
Vdd
X Y
Vdd
C2 C2
Vdd
X Y
Vdd
Vc
Vc
C1 C1
C1 C1
M1 M2
M1 M2
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Prospect(2):Prospect(2): VaractorVaractor and and VaructorVaructor
Variable Resonator: Varactor Variable Inductor: Vaructor
C2
G
Vc
C1
M1 L1
Vdd
Y
VL
L2
M1
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1.08GHz LC VCO with MIM 1.08GHz LC VCO with MIM VaractorsVaractors
TSMC CMOS 0.25um 1P5M RF/MS Process
Simulation in SpectreRFF-V curves, 3.3mAPhase Noise < -89.7dBc/Hz@10kHz
Better phase noise in LC-VCO with MIM Varactor than in one with MOS VaractorSimulation agrees well with the calculationTSMC 0.25µm 2P5M RF/MS process
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AcknowledgementsAcknowledgements
Prof. Hao Min (Adivsor), Fudan UniversityProf. Chengshou Sun, Guoquang Zhang, Feng Zhou, Wenhong Li, Fudan UniversityProf. Qianling Zhang, Junyan Ren, Zengyu Zheng, Lianxing Yang, Zhiliang Hong, Dian Zhou, Fudan UniversityProf. Lingling Sun, Jiang Hu, HIZEE University Fuxiao Li, Zhengyu Zhu, No. 55 Institute of Science and TechnologyProf. Xiaowei Sun, Rong Qian, Shanghai Institute of M.S & IT Hongyan Jian, Jie He, Shi Shu, Fengling Yang, TV Tuner GroupQiang Li, Yifeng Han, RFID Group, Haiqing Zhang, Yawei GuoMPW service at ICCSupported in part by Shanghai Science & Technology Committee under SDC Project Supported in part by Fudan-Infineon Joint Lab
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Thanks!Thanks!