12/10/2004 EE 42 fall 2004 lecture 4 2 1 Lecture #42: Transistors, digital • This week we will be reviewing the material learned during the course • Today: review – CMOS transistors – Digital logic
Dec 22, 2015
12/10/2004 EE 42 fall 2004 lecture 42 1
Lecture #42: Transistors, digital
• This week we will be reviewing the material learned during the course
• Today: review– CMOS transistors – Digital logic
12/10/2004 EE 42 fall 2004 lecture 42 2
Review Session
• When: Thursday, Dec. 16th; 3-6pm
• Where: Evans 0009
• Format: Open, bring questions
12/10/2004 EE 42 fall 2004 lecture 42 3
Final Exam
Date/Time: • SATURDAY, DECEMBER 18, 2004 • 5-8PMLocation: 150 GSPP(Goldman School of Public Policy) Format:• Closed book• One page, (two sides) of notes
12/10/2004 EE 42 fall 2004 lecture 42 4
n
P
oxide insulatorn
drain
- +
source
gate
MOS transistorBelow threshold
VGS < Vt
Below threshold, there are no electrons under the gate oxide, and the holes in the substrate are blocked from carrying current by reverse biased diode junctions
12/10/2004 EE 42 fall 2004 lecture 42 5
n
P
oxide insulatorn
drain
- +
source
gate
NMOS in the linear (Triode) region
VGS > Vt
If the gate voltage is above threshold, but the source to drain voltage is small, the charge under the gate is uniform, and carries current much like a resistor
The electrons move under the influence of the
Electric field at a velocity: ν=μE where E=volts/distance
And they must travel a distance L to cross the gate
Since the total charge is Q=CVgs, we will have a current
Id=μCgateVds (Vgs-Vth)/L2= μ(εox/dox)Vds (Vgs-Vth)W/L
12/10/2004 EE 42 fall 2004 lecture 42 6
n
P
oxide insulatorn
drain
- +
source
gate
NMOS with increasing Vds
VGS > Vt
As the voltage from the source to the drain is increased, the current increases, but not by as much because the charge is attracted out from under the oxide, beginning to pinch off the channel
12/10/2004 EE 42 fall 2004 lecture 42 7
Saturation
• As the Source-Drain voltage is increased, there will be a significant change in the charge at different distances along the gate
• When the voltage across the device at the drain end goes below threshold, the current is pinched off.
• If there is no current out the drain end, however, the current due to the carriers which are available from the source cause the voltage to be closer to that of the source.
• These two effects cause a small region to form near the drain which limits the current. This is called saturation
12/10/2004 EE 42 fall 2004 lecture 42 8
A little more MOS “Theory”
We have two regions: the resistive region at smaller VDS and the saturation region at higher VDS .
ID
VDS
VGS
In the resistive region we start out like a simple resistor between source and drain (whose value depends on gate voltage) and gradually the curve “bends over” as we approach saturation
In the saturation we have a small gradual increase of I with VDS
VGS
SG
VDS
iD+ +-
D
12/10/2004 EE 42 fall 2004 lecture 42 9
Basic CMOS Inverter
Inverter
IN OUT
VDD p-ch
VDD
OUT
IN
n-ch
CMOS Inverter
GROUND
IN
OUT
VDD
N-WELL
NMOS Gate
PMOS Gate
Al “wires”
GROUND
IN
OUT
VDD
N-WELL
NMOS Gate
PMOS Gate
Al “wires”
Example layout of CMOS Inverter
12/10/2004 EE 42 fall 2004 lecture 42 11
n-typemetal metaloxide insulator
metal
p-type
metal
gate
source
drain
n-type
- +
VGS
- +
VDS
IDIG
G
DS
ID
IG
- VDS +
+
VGS_
NMOS Transistor
12/10/2004 EE 42 fall 2004 lecture 42 12
G
DS
ID
IG
- VDS +
+
VGS_
NMOS I-V Characteristic
• Since the transistor is a 3-terminal device, there is no single I-V characteristic.
• Note that because of the insulator, IG = 0 A.
• We typically define the MOS I-V characteristic as
ID vs. VDS for a fixed VGS.
• The I-V characteristic changes as VGS changes.
12/10/2004 EE 42 fall 2004 lecture 42 13
triode mode
cutoff mode (when VGS < VTH(N))
saturation mode
VDS
ID
VGS = 3 V
VGS = 2 V
VGS = 1 V
VDS = VGS - VTH(n)
NMOS I-V Curves
12/10/2004 EE 42 fall 2004 lecture 42 14
Saturation in a MOS transistor• At low Source to drain voltages, a MOS transistor looks
like a resistor which is “turned on” by the gate voltage• If a more voltage is applied to the drain to pull more
current through, the amount of current which flows stops increasing→ an effect called pinch-off.
• Think of water being sucked through a flexible wall tube. Dropping the pressure at the end in order to try to get more water to come through just collapses the tube.
• The current flow then just depends on the flow at the input: VGS
• This is often the desired operating range for a MOS transistor (in a linear circuit), as it gives a current source at the drain as a function of the voltage from the gate to the source.
12/10/2004 EE 42 fall 2004 lecture 42 15
NAND gate
A B A B A B
Making a NAND gate: (NMOS pulls “down”, PMOS “up”)
NMOS portion: both inputs need to be high for output to be low series
CMOS DIGITAL LOGIC
0 0 0 1
0 1 0 1
1 0 0 1
1 1 1 0
PMOS portion: either input can be low for output to be high parallel
C=
B
C
A
VDD
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These are circuits that accomplish a given logic function such as “OR”. We will shortly see how such circuits are constructed. Each of the basic logic gates has a unique symbol, and there are several additional logic gates that are regarded as important enough to have their own symbol. The set is: AND, OR, NOT, NAND, NOR, and EXCLUSIVE OR.
Logic Gates
A
BC=A·BAND C =
A
BNAND BA
C = NORA
BBA
NOTA A
ORA
BC=A+B
EXCLUSIVE OR
A
BBAC
12/10/2004 EE 42 fall 2004 lecture 42 17
Transistor Inverter ExampleIt may be simpler to just think of PMOS and NMOS transistors instead
of a general 3 terminal pull-up or pull-down devices or networks.
VIN-D
Pull-Down Network VOUT
IOUT
Output
VDD
Pull-Up Network
VIN-U
VIN-D
VIN-U
VOUT
IOUT
Output
VDD
p-type MOSTransistor(PMOS)
n-type MOSTransistor(NMOS)
12/10/2004 EE 42 fall 2004 lecture 42 18
Complementary Networks
• If inputs A and B are connected to parallel NMOS, A and B must be connected to series PMOS.
• The reverse is also true.• Determining the logic function from CMOS circuit is
not hard:– Look at the NMOS half. It will tell you when the output is
logic zero.– Parallel transistors: “like or”– Series transistors: “like and”
12/10/2004 EE 42 fall 2004 lecture 42 19
Some Useful Theorems
1)
2)
3)
4)
5)
6)
7)
8)
9)
1 AA
0 AA
C)(BACABA
ABC CBA
AB BA
BABA
BABA } de Morgan’s Laws
ABC CBA
AB BA
Each of these can be proved by writing out truth tables
Communicative
Associative
Distributive
Defined from
truth tables
12/10/2004 EE 42 fall 2004 lecture 42 20
Evaluation of Logical Expressions with “Truth Tables”
The Truth Table completely describes a logic expression
In fact, we will use the Truth Table as the fundamental meaning of a logic expression.
Two logic expressions are equal if their truth tables are the same
A truth table can be turned into a sum-of-products by writing each row which results in a “1” output as an “and” (the product), and then ORing them together (the sum)
12/10/2004 EE 42 fall 2004 lecture 42 21
Going from a Boolean expression to gates
Simply expand the Boolean expression into a SUM-OF-PRODUCTS expression:
Y = ABC+DEF
Then rewrite it by “inverting” with De Morgan:
NAND GATE SYNTHESIS. Using De Morgan’s theorem we can turn any Boolean expression into NAND gates.
The NAND realization, while based on DeMorgan’s theorem, is in fact much simpler: just look at the sum of products expression and use one NAND for each term and one to combine the terms.
(DEF) (ABC)Y
AB
YC
DE
F
Clearly this expression is realized with three NAND gates: one three-input NAND for , one for
, and one two-input gate to combine them:(ABC)
(DEF)
12/10/2004 EE 42 fall 2004 lecture 42 22
Synthesis
Designing the combinatorial logic circuit, con’t
Two Examples of SUM-OF-PRODUCTS expressions:
Method 3: NAND GATE SYNTHESIS (CONTINUED).
BABA X (X-OR function)
A
X
B
(No connection)
CBAABCY
A
Y
B C
We could make the drawings simpler by just using a circle for the NOT function rather than showing a one-input NAND gate
12/10/2004 EE 42 fall 2004 lecture 42 23
NMOS switches in series from output to ground; PMOS switches in parallel from output to the supply (Here we left out the A-A and B-B connection for clarity)
CMOS NAND GATE
vA
vB
vOUT
VDD
vA vB
Behaves like 2 Rn’s in series
when both A and B are high
NAND: If either output is low then one of the bottom (pull down) series switches is open and one of the upper (pull up) switches are closed.
Thus the output is pulled high.
12/10/2004 EE 42 fall 2004 lecture 42 24
NAND Gate Pull-Up Model*
vOUT
VDD
vA vB
vA
vB
pR pR
CGpGn CCC
= RC = RpC )CC(R GpGnp
One or both switches closed (worse case: one switch)
Output is loaded by the gate capacitance of the next stage: C= CGn+CGp
12/10/2004 EE 42 fall 2004 lecture 42 25
B
F
A
VDD
C
F
A
VDD
B
NAND Gates with more inputs
2-input NAND
Each input loads with CGN +CGP
Output drives with 2RDN or RDP
3-input NAND
Each input loads with CGN +CGP
Output drives with 3RDN or RDP
12/10/2004 EE 42 fall 2004 lecture 42 26
NOR function (two inputs)
A B A +B C=A +B
Output is low if either input is high
NMOS switches (between ground and the output) in parallel
CMOS NOR GATE
0 0 0 1
0 1 1 0
1 0 1 0
1 1 1 0
BAOutput is high only if both inputs are low
PMOS switches (between the supply and the output) in series
VDD
A
BC
12/10/2004 EE 42 fall 2004 lecture 42 27
“Complementary” configuration to the NAND gate
CMOS NOR GATE
vOUT
VDD
vA
vB
vOUT
VDD
vA
vB
NOR NAND
12/10/2004 EE 42 fall 2004 lecture 42 28
Definition of Fanout
Fanout = number of gates that are connected to the driver
Fanout leads to increased capacitive load (and higher delay)
12/10/2004 EE 42 fall 2004 lecture 42 29
Clocked logic
• If we put two latches into every feedback path, and make sure both latches are never open at the same time, we can insure predicable results.
A
B
C Outputs
12/10/2004 EE 42 fall 2004 lecture 42 30
Edge trigger
• If we use an edge trigger, then a single phase clock can be used. An edge triggered flip flop will only change at a rising or falling edge of the clock, so that the new state will not feedback to its own value
A
B
C Outputs
trigger edge
12/10/2004 EE 42 fall 2004 lecture 42 31
Sequential logic
• The timing rules for sequential logic can be summarized:
• Only one transition of the latches are allowed per clock cycle, the change from one clock is not allowed to circulate back through the logic to effect itself.
• The clock speed will be limited by the slowest path
• The fastest path must not be allowed to change the state before changes have been latched out