Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf Topics n Interconnect design. n Crosstalk. n Power optimization.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Topics

Interconnect design. Crosstalk. Power optimization.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Interconnect

Even assuming logic structure is fixed, we can:– change wire topology;– resize wires;– add buffers;– size transistors.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Multipoint nets

Two-point nets are easy to design. Multipoint nets are harder:

– How do we connect all the pins using two-point connections?

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Styles of wiring trees

source

sink 2

sink 1

Spanning tree

Steiner treeSteiner point

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Sized Steiner tree

source

sink 2

sink 1

Feeds both branches

Smaller currents in each branch

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Buffer insertion in wiring trees

More complex than placing buffers along a transmission line:– complex topology;– unbalanced trees;– differing timing requirements at the leaves.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Van Ginneken algorithm

Given:– placements of sources and sinks;– routing of wiring tree.

Place buffers within tree to minimize the departure time at the source to meet all the sink arrival times:– Tsource = min i (T i -D i)

– T i = arrival time at node i, D i = delay to node I.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Delay calculation

Use Elmore model to compute delay along path from source to sink.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Recursive delay calculation

Recursively compute Elmore delay through the tree.– Start at sinks, work back to source.– r, c are unit resistance/capacitance of wire.

– Lk is total capacitive load of subtree rooted at node k.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Modifying the tree

Add a wire of length l at node k:– Tk’ = Tk - r/Lk - 0.5rcl.

– Lk’ = Lk + cl.

Buffer node k:– Tk’ = Tk - Dbuf - Rbuf Lk.

– Lk’ = Cbuf.

Join two subtrees m and n at node k:– Tk’ = (Tm , Tn).

– Lk’ = Lm + Ln.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Crosstalk

Capacitive coupling introduces crosstalk. Crosstalk slows down signals to static gates,

can cause hard errors in storage nodes. Crosstalk can be controlled by

methodological and optimization techniques.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Interleaved power/ground

VDD

VSS

VDD

VSS

VDD

VSS

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Twizzled wires

a

b

c

d

b

d

a

c

a

b

c

d

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Coupling and crosstalk

Crosstalk current depends on capacitance, voltage ramp.

w1 w2

Cc

ic

t

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Crosstalk analysis

Assume worst-case voltage swings, signal slopes.

Measure coupling capacitance based on geometrical alignment/overlap.

Some nodes are particularly sensitive to crosstalk:– dynamic;– asynchronous.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Coupling situations

sig1a x r

better worse

bus[0]

bus[1]

bus[2]

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Layer-to-layer coupling

Long parallel runs on adjacent layers are also bad.

bus[0]

siga

SiO2

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Methodological solutions

Add ground wires between signal wires:– coupling to VSS, a stable signal, dominates;

– can use VSS to distribute power, so long as power line is relatively stable.

Extreme case—add ground plane. Costs an entire layer, may be overkill.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Ground wires

VSS

sig1

VSS

sig2

VSS

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Crosstalk and signal routing

Can route wires to minimize required adjacency regions.

Take advantage of natural holes in routing areas to decouple signals.

Minimizes need for ground signals.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Assumptions

Take into account coupling only to wires in adjacent tracks.

Ignore coupling of vertical wires. Assume that coupling/crosstalk is

proportional to adjacency length.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Crosstalk example

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Crosstalk analysis

Want to estimate delays induced by crosstalk.

Effect of coupling capacitance Cc depends on relative transitions.– Aggressor changes, victim does not: Cc.

– Aggressor, victim move in opposite directions: 2Cc.

– Aggressor, victim move in same direction: 0.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Crosstalk analysis, cont’d.

Coupling effects depend on relative switching time of nets.

Must use iterative algorithm to solve for coupling capacitances and delays.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Power optimization

Glitches cause unnecessary power consumption.

Logic network design helps control power consumption:– minimizing capacitance;– eliminating unnecessary glitches.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Glitching example

Gate network:

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Glitching example behavior

NOR gate produces 0 output at beginning and end:– beginning: bottom input is 1;– end: NAND output is 1;

Difference in delay between application of primary inputs and generation of new NAND output causes glitch.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Adder chain glitching

bad good

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Explanation

Unbalanced chain has signals arriving at different times at each adder.

A glitch downstream propagates all the way upstream.

Balanced tree introduces multiple glitches simultaneously, reducing total glitch activity.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Signal probabilities

Glitching behavior can be characterized by signal probabilities.

Transition probabilities can be computed from signal probabilities if clock cycles are assumed to be independent.

Some primary inputs may have non-standard signal probabilities— control signal may be activated only occasionally.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Delay-independent probabilities

Compute output probabilities of primitive functions:– PNOT = 1 - Pin

– POR = 1 - Pi)

– PAND = Pi

Can compute output probabilities of reconvergent fanout-free networks by traversing tree.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Delay-dependent probabilities

More accurate estimation of glitching. Glitch accuracy depends on accuracy of delay model.

Can use simulation-style algorithms to propagate glitches.

Can use statistical models coupled with delay models.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Power estimation tools

Power estimator approximates power consumption from:– gate network;– primary input transition probabilities;– capacitive loading.

May be switch/logic simulation based or use statistical models.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Factorization for low power

Proper factorization reduces glitching.

bad good

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Factorization techniques

In example, a has high transition probability, b and c low probabilities.

Reduce number of logic levels through which high-probability signals must travel in order to reduce propagation of glitches.

Modern VLSI Design 4e: Chapter 4 Copyright 2008 Wayne Wolf

Layout for low power

Place and route to minimize capacitance of nodes with high glitching activity.

Feed back wiring capacitance values to power analysis for better estimates.